lt3477 – 3a, dc/dc converter with dual rail-to-rail current sense · 2020. 2. 1. · 3477 g14 100...
TRANSCRIPT
LT3477
13477fd
For more information www.linear.com/LT3477
Typical applicaTion
DescripTion
3A, DC/DC Converter with Dual Rail-to-Rail
Current SenseFeaTures
applicaTions
n Dual 100mV Rail-to-Rail Current Sense Amplifiers n Wide Input Voltage Range: 2.5V to 25V n 3A, 42V Internal Switch n High Efficiency Power Conversion: Up to 93% n Drives LEDs in Boost, Buck-Boost or Buck Mode n Frequency Set by External Resistor: 200kHz to 3.5MHz n Programmable Soft-Start n Low VCESAT Switch: 0.3V at 2.5A n Capable of Positive and Negative Output Voltages
(Boost, Inverting, SEPIC, Flyback) n Available in Thermally Enhanced 20-Lead
(4mm × 4mm) QFN and 20-Lead TSSOP Packages
The LT®3477 is a current mode, 3A DC/DC step-up converter with dual rail-to-rail current sense amplifiers and an internal 3A, 42V switch. It combines a traditional voltage feedback loop and two unique current feedback loops to operate as a constant-current, constant-voltage source. Both cur-rent sense voltages are set at 100mV and can be adjusted independently using the IADJ1 and IADJ2 pins. Efficiency of up to 93% can be achieved in typical applications. The LT3477 features a programmable soft-start function to limit inductor current during start-up. Both inputs of the error amplifier are available externally allowing positive and negative output voltages (boost, inverting, SEPIC, Flyback). The switching frequency is programmable from 200kHz to 3.5MHz through an external resistor.
Available in thermally enhanced 20-pin (4mm × 4mm) QFN and 20-pin TSSOP packages, the LT3477 provides a complete solution for both constant-voltage and constant-current applications.
Efficiency330mA LED Driver With Open LED Protection
ISN1ISP1
VINIADJ1IADJ2
FBN
ISP2
200k3.3µF3.3µF
VIN5V
33nF4.7nF
330mA
3477 TA01a
10k
22k
1k
0.3Ω
SW
10µH
FBP SSGND
LT3477
ISN2
RT
SHDN
VC
VREF
SHDN
IOUT (A)0
EFFI
CIEN
CY (%
)
70
75
80
0.4
3477 TA01b
65
60
500.1 0.2 0.3
55
90
85
n High Power LED Driver n DSL Modems n Distributed Power n Input/Output Current Limited Boost, SEPIC,
Inverting, Flyback Converters n Constant-Voltage, Constant-Current Source
, LT, LTC and LTM are registered trademarks of Linear Technology Corporation.All other trademarks are the property of their respective owners.
LT3477
23477fd
For more information www.linear.com/LT3477
absoluTe MaxiMuM raTingsSW Pin Voltage ........................................................ 42VVIN, SHDN Pin Voltage ............................................. 25VFBP, FBN Pin Voltage ................................................. 6VVREF Pin Voltage......................................................... 6VRT, VC, SS Pin Voltage ............................................... 6VIADJ1, IADJ2 Pin Voltage ............................................ 25VISP1, ISP2, ISN1, ISN2 Pin Voltage ...............................42V
(Note 1)
Junction Temperature .......................................... 125°COperating Temperature Range (Note 2) LT3477E ...............................................– 40°C to 85°C LT3477I .............................................. –40°C to 125°CStorage Temperature Range ...................–65°C to 125°CLead Temperature (Soldering, 10 sec) TSSOP .............................................................. 300°C
FE PACKAGE20-LEAD PLASTIC TSSOP
1
2
3
4
5
6
7
8
9
10
TOP VIEW
20
19
18
17
16
15
14
13
12
11
VIN
RT
SHDN
SS
VC
FBN
FBP
VREF
IADJ2
IADJ1
NC
NC
NC
SW
SW
GND
ISN1
ISP1
ISN2
ISP2
21
TJMAX = 125°C, θJA = 40°C/W
EXPOSED PAD (PIN 21) IS PGND (MUST BE SOLDERED TO PCB)
20 19 18 17 16
6 7 8
TOP VIEW
21
UF PACKAGE20-LEAD (4mm × 4mm) PLASTIC QFN
9 10
5
4
3
2
1
11
12
13
14
15NC
NC
VIN
RT
SHDN
ISP1
ISN2
ISP2
IADJ1
IADJ2
NC SW SW GND
I SN1
SS V C FBN
FBP
V REF
TJMAX = 125°C, θJA = 37°C/W
EXPOSED PAD (PIN 21) IS PGND (MUST BE SOLDERED TO PCB)
LEAD FREE FINISH TAPE AND REEL PART MARKING PACKAGE DESCRIPTION TEMPERATURE RANGE
LT3477EFE#PBF LT3477EFE#TRPBF 20-Lead Plastic TSSOP –40°C to 85°C
LT3477IFE#PBF LT3477IFE#TRPBF 20-Lead Plastic TSSOP –40°C to 125°C
LT3477EUF#PBF LT3477EUF#TRPBF 3477 20-Lead (4mm × 4mm) Plastic QFN –40°C to 85°C
LT3477IUF#PBF LT3477IUF#TRPBF 3477 20-Lead (4mm × 4mm) Plastic QFN –40°C to 125°C
Consult LTC Marketing for parts specified with wider operating temperature ranges.For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifications, go to: http://www.linear.com/tapeandreel/. Some packages are available in 500 unit reels through designated sales channels with #TRMPBF suffix.
pin conFiguraTion
orDer inForMaTion http://www.linear.com/product/LT3477#orderinfo
LT3477
33477fd
For more information www.linear.com/LT3477
elecTrical characTerisTics The l indicates specifications which apply over the full operating temperature range, otherwise specifications are at TA = 25°C. VIN = 2.5V, VSHDN = 2.5V.PARAMETER CONDITIONS MIN TYP MAX UNITS
Minimum Input Voltage l 2.3 2.5 V
Quiescent Current VSHDN = 0V VSHDN = 2.5V, VC = 0.3V (Not Switching)
0.1 5.0
1.0 7.5
µA mA
Reference Voltage E Grade I Grade
l
l
1.216 1.210
1.235 1.235
1.250 1.260
V V
Reference Voltage Line Regulation 2.5V < VIN < 25V, VC = 0.3V 0.01 0.03 %/V
Maximum VREF Pin Current Out of Pin 100 µA
Soft-Start Pin Current SS = 0.5V, Out of Pin 9 µA
FBP Pin Bias Current 25 100 nA
FBN Pin Bias Current 25 100 nA
Feedback Amplifier Offset Voltage FBP – FBN, VC = 1V –2 2 6 mV
Feedback Amplifier Voltage Gain 500 V/V
Voltage Feedback Amplifier Transconductance 500 µS
Feedback Amplifier Sink Current VFBP = 1.25V, VFBN = 1.5V, VC = 1V 10 µA
Feedback Amplifier Source Current VFBP = 1.25V, VFBN = 1V, VC = 0.5V 10 µA
Current Sense Amplifier Sense Voltage Positive Rail, VCM = 25V, E Grade Positive Rail, VCM = 25V, I Grade Ground
l
l
97.5 97.5 88
100 100 100
102.5 103 112
mV mV mV
Switching Frequency RT = 17.2k RT = 107.4k RT = 2.44k
0.9 160 2.7
1 200 3.5
1.15 240 4.3
MHz kHz
MHz
Maximum Switch Duty Cycle RT = 17.2k l 87 93 %
Switch Current Limit (Note 3) 3 4 5 A
Switch VCESAT ISW = 1A (Note 3) 150 200 mV
Switch Leakage Current SW = 40V 0.2 5 µA
SHDN Pin Current VSHDN = 5V VSHDN = 0V
30 0.1
60 1
µA µA
SHDN Pin Threshold 0.3 1.5 2 V
Note 1: Stresses beyond those listed under Absolute Maximum Ratings may cause permanent damage to the device. Exposure to any Absolute Maximum Rating condition for extended periods may affect device reliability and lifetime.Note 2: The LT3477E is guaranteed to meet performance specifications from 0°C to 70°C. Specifications over the –40°C to 85°C operating
junction temperature range are assured by design, characterization and correlation with statistical process controls. The LT3477I is guaranteed over the full –40°C to 125°C operating junction temperature range.Note 3: Switch current limit and switch VCESAT for UF package guaranteed by design and/or correlation to static test.
LT3477
43477fd
For more information www.linear.com/LT3477
TEMPERATURE (°C)–50
SHDN
THR
ESHO
LD (V
)
1.4
1.6
25 75
3477 G04
1.2
–25 0 50 100 1251.0
VSHDN (V)0
SHDN
PIN
CUR
RENT
(µA)
30
40
50
20
3477 G05
20
10
05 10 15
–50°C
25°C
125°C
25TEMPERATURE (°C)
–502
QUIE
SCEN
T CU
RREN
T (m
A)
3
4
5
6
–25 0 25 50
3477 G06
75 100 125 150
VC = 0.3V
TEMPERATURE (°C)–50
0
I SS
(µA)
5
10
15
20
–25 0 25 50
3477 G07
75 100 125 150
TEMPERATURE (°C)–50
FREQ
UENC
Y (M
Hz)
1.2
1.6
2.0
25 75 150
3477 G08
0.8
0.4
0–25 0 50 100 125
RT = 10kΩ
RT = 15kΩ
RT = 20kΩ
TEMPERATURE (°C)–50
OFFS
ET V
OLTA
GE (m
V)
0
2
150
3477 G09
–2
–40 50 100–25 25 75 125
4
–1
1
–3
3
VC = 1V
VC = 0.5V
Typical perForMance characTerisTics
Soft-Start Pin Current Oscillator Frequency Feedback Amplifier Offset Voltage
SHDN Pin Turn-On Threshold SHDN Pin Current Quiescent Current
Switch VCE(SAT) Switch Current Limit VREF
SWITCH CURRENT (A)0
0
V CE(
SAT)
(V)
0.10
0.20
0.30
0.25
0.5 1 1.5 2
3477 G01
2.5
0.40
0.50
0.05
0.15
125°C
–50°C
0.35
0.45
3
25°C
TEMPERATURE (°C)–50 –25
0
CURR
ENT
(A)
2
5
0 50 75
3477 G02
1
4
3
25 100 125TEMPERATURE (°C)
–501.21
V REF
(V)
1.22
1.23
1.24
1.25
0 50 100 150
3477 G03
1.26
1.27
–25 25 75 125
VIN = 25V
VIN = 2.5V
LT3477
53477fd
For more information www.linear.com/LT3477
IADJ VOLTAGE (mV)0
0
VOLT
AGE
SENS
E (m
V)
20
40
60
80
200 400 600 800
2477 G13
100
120
100 300 500 700
VCM = 10V
TEMPERATURE (°C)–50
CURR
ENT
SENS
E VO
LTAG
E (m
V)
103
25
3477 G14
100
98
–25 0 50
97
96
104
102
101
99
75 100 125
VCM = 10V
VCM = 42V
TEMPERATURE (°C)–50
FBP
PIN
BIAS
CUR
RENT
(nA)
30
40
50
25 75
3477 G10
20
10
–25 0 50 100 125
0
–10
“+” INDICATES THE CURRENT FLOWS OUT OF PIN
TEMPERATURE (°C)–50
FBN
PIN
BIAS
CUR
RENT
(nA)
30
40
50
25 75
3477 G11
20
10
–25 0 50 100 125
0
–10
“+” INDICATES THE CURRENT FLOWS OUT OF PIN
Typical perForMance characTerisTics
FBP Pin Bias Current FBN Pin Bias Current
Current Sense Voltage vs IADJ
Current Sense Voltage vs Temperature
LT3477
63477fd
For more information www.linear.com/LT3477
pin FuncTions (QFN/TSSOP)
NC (Pins 1, 2, 20/Pins 18, 19, 20): No Connect Pin. Okay to connect to ground or VIN, or to float.
VIN (Pin 3/Pin 1): Input Supply. Must be locally bypassed. Powers the internal control circuitry.
RT (Pin 4/Pin 2): Timing Resistor Pin. Adjusts the switch-ing frequency. Connect a 17.2k resistor between RT and GND for a 1MHz switching frequency. Do not leave this pin open. See Table 4 for additional RT values and switching frequencies.
SHDN (Pin 5/Pin 3): Shutdown. Tie to 2V or greater to enable the device. Tie below 0.3V to turn off the device.
SS (Pin 6/Pin 4): Soft-Start. Place a soft-start capacitor here. Leave floating if not in use.
VC (Pin 7/Pin 5): Compensation Pin for Error Amplifier. Connect a series RC from this pin to GND. Typical values are 1kΩ and 4.7nF.
FBN (Pin 8/Pin 6): The Inverting Input to the Error Ampli-fier. Connect resistive divider tap here for positive output voltage.
FBP (Pin 9/Pin 7): The Noninverting Input to the Error Amplifier. Connect resistive divider tap here for negative output voltage.
VREF (Pin 10/Pin 8): Bandgap Voltage Reference. Internally set to 1.235V. Connect this pin to FBP if generating a posi-tive output or to an external resistor divider if generating a negative voltage. This pin can provide up to 100µA of current and can be locally bypassed with a 100pF capacitor.
IADJ2 (Pin 11/Pin 9): Second Current Sense Adjustment. Setting IADJ2 to be less than 625mV leads to adjustment of the sensed voltage of the second current sense amplifier
linearly. If IADJ2 is tied to higher than 650mV, the default current sense voltage is 100mV. If current sense ampli-fier 2 is not used, always tie IADJ2 to higher than 650mV.
IADJ1 (Pin 12/Pin 10): First Current Sense Adjustment. Setting IADJ1 to be less than 625mV leads to adjustment of the sensed voltage of the first current sense amplifier linearly. If IADJ1 is tied to higher than 650mV, the default current sense voltage is 100mV. If current sense ampli-fier 1 is not used, always tie IADJ1 to higher than 650mV.
ISP2 (Pin 13/Pin 11): Second Current Sense (+) Pin. The noninverting input to the second current sense amplifier. Connect to ISN2 if not used.
ISN2 (Pin 14/Pin 12): Second Current Sense (–) Pin. The inverting input to the second current sense amplifier. Con-nect to ISP2 if not used.
ISP1 (Pin 15/Pin 13): First Current Sense (+) Pin. The noninverting input to the first current sense amplifier. Connect to ISN1 if not used.
ISN1 (Pin 16/Pin 14): First Current Sense (–) Pin. The in-verting input to the first current sense amplifier. Connect to ISP1 if not used.
GND (Pins 17/Pin 15): Ground. Tie directly to local ground plane.
SW (Pins 18, 19/Pins 16, 17): Switch Pins. Collector of the internal NPN power switch. Connect the inductor and diode here and minimize the metal trace area connected to this pin to minimize electromagnetic interference.
Exposed Pad (Pin 21/Pin 21): Power Ground. Must be soldered to PCB ground for electrical contact and rated thermal performance.
LT3477
73477fd
For more information www.linear.com/LT3477
–
+
–
+
–
+
∑
–++
IA1
ISP1
ISN1A1
VC SWSS
A3
A4SLOPE
VADJ
IADJ1
ISP2
ISN2
FBP
FBN
SHDN
IADJ2
VREF
–
+–++
IA2
–
+
RTVIN
VA
A2VADJ
VREF1.235V
SR Q1
3477 F01
Q
OSCILLATOR
Figure 1. LT3477 Block Diagram
blocK DiagraM
LT3477
83477fd
For more information www.linear.com/LT3477
operaTionThe LT3477 uses a fixed frequency, current mode control scheme to provide excellent line and load regulation. Op-eration can be best understood by referring to the Block Diagram in Figure 1. The start of each oscillator cycle sets the SR latch and turns on power switch Q1. The signal at the noninverting input of the PWM comparator (A4 SLOPE) is proportional to the sum of the switch current and oscillator ramp. When SLOPE exceeds VC (the output of the feedback amplifier), the PWM comparator resets the latch and turns off the power switch. In this manner, the feedback amplifier and PWM comparators set the correct peak current level to keep the output in regulation. Amplifier A3 drives A4 inverting input. A3 has three inputs, one from the voltage feedback loop and the other two from the current feedback loop. Whichever feedback input is higher takes precedence, forcing the converter into either a constant-current or a constant-voltage mode. The LT3477 is designed to transi-tion cleanly between the two modes of operation. Current sense amplifier IA1 senses the voltage between the ISP1 and ISN1 pins and provides a pre-gain to amplifier A1. When the voltage between ISP1 and ISN1 reaches 100mV, the output of IA1 provides VADJ to the inverting input of A1 and the converter is in constant-current mode. If the current sense voltage exceeds 100mV, the output of IA1 will increase causing the output of A3 to decrease, thus reducing the amount of current delivered to the output.
In this manner the current sense voltage is regulated to 100mV. The current sense level is also pin adjustable by IADJ1. Forcing IADJ1 to less than 625mV will overwrite VADJ voltage that’s set internally, thus providing current level control. The second current sense amplifier, IA2, works the same as the first current sense amplifier IA1. Both current sense amplifiers provide rail-to-rail current sense operation. Similarly, for positive output voltage operation where FBP is tied to VREF, if the FBN pin increases above VREF, the output of A3 will decrease to reduce the peak current level and regulate the output (constant-voltage mode). For negative output voltage operation where FBN is tied to GND, if the FBP pin decreases below GND level, the output of A3 will decrease to reduce the peak current level and regulate the output (constant-voltage mode).
The LT3477 also features a soft-start function. During start-up, 9µA of current charges the external soft-start capacitor. The SS pin directly limits the rate of voltage rise on the VC pin, which in turn limits the peak switch cur-rent. The switch current is constantly monitored and not allowed to exceed the nominal value of 3A. If the switch current reaches 3A, the SR latch is reset regardless of the output of the PWM comparator. Current limit protects the power switch and external components.
LT3477
93477fd
For more information www.linear.com/LT3477
applicaTions inForMaTionCapacitor Selection
Low ESR (equivalent series resistance) ceramic capaci-tors should be used at the output to minimize the output ripple voltage. Use only X5R or X7R dielectrics, as these materials retain their capacitance over wider voltage and temperature ranges better than other dielectrics. A 4.7µF to 10µF output capacitor is sufficient for most high output current designs. Converters with lower output currents may need only a 1µF or 2.2µF output capacitor.
Table 1. Ceramic Capacitor ManufacturersMANUFACTURER PHONE WEB
Taiyo Yuden (408) 573-4150 www.t-yuden.com
AVX (803) 448-9411 www.avxcorp.com
Murata (714) 852-2001 www.murata.com
TDK (847) 803-6100 www.component.tdk.com
Inductor Selection
Several inductors that work well with the LT3477 are listed in Table 2. However, there are many other manufacturers and devices that can be used. Consult each manufacturer for more detailed information and their entire range of parts. Ferrite core inductors should be used to obtain the best efficiency. Choose an inductor that can handle the necessary peak current without saturating, and ensure that the inductor has a low DCR (copper-wire resistance) to minimize I2R power losses. A 4.7µH or 10µH inductor will suffice for most LT3477 applications.
Inductor manufacturers specify the maximum current rating as the current where the inductance falls to some
percentage of its nominal value—typically 65%. An inductor can pass a current larger than its rated value without damaging it. Aggressive designs where board space is precious will exceed the maximum current rat-ing of the inductor to save board space. Consult each manufacturer to determine how the maximum inductor current is measured and how much more current the inductor can reliably conduct.
Diode Selection
Schottky diodes, with their low forward voltage drop and fast switching speed, are ideal for LT3477 applications. Table 3 lists several Schottky diodes that work well with the LT3477. The diode’s average current rating must exceed the average output current. The diode’s maximum reverse voltage must exceed the output voltage. The diode conducts current only when the power switch is turned off (typically less than 50% duty cycle), so a 3A diode is sufficient for most designs. The companies below also offer Schottky diodes with higher voltage and current ratings.
Table 3. Suggested DiodesMANUFACTURER PART NUMBER
MAX CURRENT (A)
MAX REVERSE VOLTAGE (V)
MANUFACTURER
UPS340 UPS315
n 3 3
n 40 15
Microsemi www.microsemi.com
B220 B230 B240 B320 B330 B340 SBM340
n 2 2 2 3 3 3 3
n 20 30 40 20 30 40 40
Diodes, Inc www.diodes.com
Table 2. Suggested InductorsMANUFACTURER PART NUMBER
IDC (A)
INDUCTANCE (µH)
MAX DCR (mΩ)
L × W × H (mm)
MANUFACTURER
CDRH6D283R0 CDRH6D28100 CDRH4D284R7
3 1.7 1.32
3 10 4.7
24 65 72
6.7 × 6.7 × 3.0 6.7 × 6.7 × 3.0 5.0 × 5.0 × 3.0
Sumida www.sumida.com
LM N 05D B4R7M LM N 05D B100K
2.2 1.6
4.7 10
49 10
5.9 × 6.1 × 2.8 5.9 × 6.1 × 2.8
Taiyo Yuden www.t-yuden.com
LQH55DN4R7M01L LQH55DN100M01K
2.7 1.7
4.7 10
57 130
5.7 × 5.0 × 4.7 5.7 × 5.0 × 4.7
Murata www.murata.com
FDV0630-4R7M 4.2 4.7 49 7.0 × 7.7 × 3.0 Toko www.toko.com
LT3477
103477fd
For more information www.linear.com/LT3477
applicaTions inForMaTionSetting Positive Output VoltagesTo set a positive output voltage, select the values of R1 and R2 (see Figure 2) according to the following equation:
VOUT = 1.235V 1+ R1
R2⎛
⎝⎜
⎞
⎠⎟
For designs needing an adjustable current level, the IADJ1 and IADJ2 pins are provided for the first and the second current sense amplifiers, respectively. With the IADJ1 and IADJ2 pins tied higher than 650mV, the nominal current sense voltage is 100mV (appearing between the ISP1 and ISN2 or ISP2 and ISN2 pins). Applying a positive DC voltage less than 600mV to the IADJ1 and IADJ2 pins will decrease the current sense voltage according to the following formula:
ISENSE =
100mVRSENSE
• VADJ618mV
For example, if 309mV is applied to the IADJ1 pin and RSENSE is 0.5Ω, the current sense will be reduced from 200mA to 100mA. The adjustability allows the regulated current to be reduced without changing the current sense resistor (e.g., to adjust brightness in an LED driver or to reduce the charge current in a battery charger).
Considerations When Sensing Input Current
In addition to regulating the DC output current for current-source applications, the constant-current loop of the LT3477 can also be used to provide an accurate input current limit. Boost converters cannot provide output short-circuit protection, but the surge turn-on current can be drastically reduced using the LT3477 current sense at the input. SEPICs, however, have an output that is DC-isolated from the input, so an input current limit not only helps soft-start the output but also provides excellent short-circuit protection.
When sensing input current, the sense resistor should be placed in front of the inductor (between the decoupling capacitor and the inductor). This will regulate the average inductor current and maintain a consistent inductor ripple current, which will, in turn, maintain a well regulated input current. Do not place the sense resistor between the input source and the input decoupling capacitor, as this may allow the inductor ripple current to vary widely (even though the average input current and the average inductor current will still be regulated). Since the inductor current is a triangular waveform (not a DC waveform like the output current) some tweaking of the compensation values (RC and CC
Figure 2. Positive Output Voltage Feedback Connections
R4
R3
3477 F03
FBP
VREF
–VOUT
LT3477
FBN
Figure 3. Negative Output Voltage Feedback Connections
R2
R1
3477 F02
FBN
VREF
VOUTLT3477
FBP
Setting Negative Output Voltages
To set a negative output voltage, select the values of R3 and R4 (see Figure 3) according to the following equation:
VOUT = 1.235V 1+R3
R4⎛
⎝⎜
⎞
⎠⎟
Selecting RSENSE/Current Sense Adjustment
Using the following formula to choose the correct cur-rent sense resistor value (for constant current or fail-safe operation).
RSENSE =
100mVISENSE
LT3477
113477fd
For more information www.linear.com/LT3477
on the VC pin) may be required to ensure a clean inductor ripple current while the constant-current loop is in effect. For these applications, the constant-current loop response can usually be improved by reducing the RC value or by adding a capacitor (with a value of approximately CC/10) in parallel with the RC and CC compensation network.
Frequency Compensation
The LT3477 has an external compensation pin (VC), which allows the loop response to be optimized for each applica-tion. An external resistor and capacitor (or sometimes just a capacitor) are placed at the VC pin to provide a pole and a zero (or just a pole) to ensure proper loop compensation. Several other poles and zeroes are present in the closed-loop transfer function of a switching regulator, so the VC pin pole and zero are positioned to provide the best loop response. A thorough analysis of the switching regulator control loop is not within the scope of this data sheet, and will not be presented here, but values of 1k and 4.7nF will be a good choice for many designs. For those wishing to optimize the compensation, use the 1k and 4.7nF as a starting point.
Board Layout
As with all switching regulators, careful attention must be paid to the PCB board layout and component place-ment. To maximize efficiency, switch rise and fall times are made as short as possible. To prevent radiation and high frequency resonance problems, proper layout of the high frequency switching path is essential. Minimize the length and area of all traces connected to the SW pin and always use a ground plane under the switching regulator to minimize interplane coupling. The signal path including the switch, output diode D1 and output capacitor COUT, contains nanosecond rise and fall times and should be kept as short as possible.
Soft-Start
For many applications, it is necessary to minimize the inrush current at start-up. The built-in soft-start circuit significantly reduces the start-up current spike and out-put voltage overshoot. A typical value for the soft-start capacitor is 10nF.
Switching Frequency
The switching frequency of the LT3477 is set by an ex-ternal resistor attached to the RT pin. Do not leave this pin open. A resistor must always be connected for proper operation. See Table 4 and Figure 4 for resistor values and corresponding frequencies.
Increasing switching frequency reduces output voltage ripple but also reduces efficiency. The user should set the frequency for the maximum tolerable output voltage ripple.
Figure 4. Switch Frequency
RT (kΩ)
0
1.5
1.0
0.5
3.5
3.0
2.5
2.0
3477 F04
SWIT
CH F
REQU
ENCY
(MHz
)
0.1 10010
applicaTions inForMaTion
Table 4. Switching FrequencySWITCHING FREQUENCY (MHz) RT (kΩ)
n 3.5 n 2.43 n 3 n 3.65 n 2.5 n 4.87 n 2 n 6.81 n 1.5 n 10.2 n 1 n 17.4 n 0.5 n 43.2 n 0.2 n 107
LT3477
123477fd
For more information www.linear.com/LT3477
applicaTions inForMaTionPWM Dimming
For LED applications where a wide dimming range is required, two competing methods are available: analog dimming and PWM dimming. The easiest method is to simply vary the DC current through the LED—analog dimming—but changing LED current also changes its chromaticity, undesirable in many applications. The bet-ter method is PWM dimming, which switches the LED on and off, using the duty cycle to control the average current. PWM dimming offers several advantages over analog dimming and is the method preferred by LED manufacturers. By modulating the duty cycle of the PWM signal, the average LED current changes proportionally as illustrated in Figure 5. The chromaticity of the LEDs remains unchanged in this scheme since the LED current is either zero or at programmed current. Another advantage of PWM dimming over analog dimming is that a wider dimming range is possible.
The LT3477 is a DC/DC converter that is ideally suited for LED applications. For the LT3477, analog dimming offers a dimming ratio of about 10:1; whereas, PWM dimming with the addition of a few external components results in a wider dimming range of 500:1. The technique requires a PWM logic signal applied to the gate of both NMOS (refer to Figure 7). When the PWM signal is taken high the part runs in normal operation and ILED = 100mV/RSENSE runs
through the LEDs. When the PWM input is taken low, the LEDs are disconnected and turn off. This unique external circuitry produces a fast rise time for the LED current, resulting in a wide dimming range of 500:1 at a PWM frequency of 100Hz.
The LED current can be controlled by feeding a PWM signal with a broad range of frequencies. Dimming below 80Hz is possible, but not desirable, due to perceptible flashing of LEDs at lower PWM frequencies. The LED current can be controlled at higher frequencies, but the dimming range decreases with increasing PWM frequency, as seen in Figure 6.
PWM dimming can be used in boost (shown in Figure 7), buck mode (shown in Figure 8) and buck-boost mode (shown in Figure 9). For the typical boost topology, ef-ficiency exceeds 80%. Buck mode can be used to increase the power handling capability for higher current LED applications. A buck-boost LED driver works best in ap-plications where the input voltage fluctuates to higher or lower than the total LED voltage drop.
In high temperature applications, the leakage of the Schottky diode D1 increases, which in turn, discharges the output capacitor during the PWM off time. This results in a smaller effective LED dimming ratio. Consequently, the dimming range decreases to about 200:1 at 85°C.
Figure 5. LED Current vs PWM Duty Cycle Wide Dimming Range (500:1)
Figure 6. Dimming Range vs PWM Frequency
PWM DUTY CYCLE (%)
0.1
LED
CURR
ENT
(mA)
1
10
100
1 10 100
3477 F05
0.010.1
VIN = 5VBOOST 4 LEDsPWM FREQUENCY = 100Hz
RT = 6.81k
PWM FREQUENCY (kHz)
0.11
DIM
MIN
G RA
NGE:
1 100
1000
1 10 100
3477 F06
10
RT = 6.81k
LT3477
133477fd
For more information www.linear.com/LT3477
applicaTions inForMaTion
Figure 7c. Efficiency and LED Currentvs PWM Duty Cycle
Figure 7b. PWM Dimming Waveforms
10µs/DIV
ILED200mA/DIV
IL1A/DIV
PWM5V/DIV
3477 F07b
VIN = 5V4 LEDs300mA
PWM FREQ = 100HzBOOST
PWM DUTY CYCLE (%)0
75
80
85
80
3477 F07c
70
65
20 40 60 100
60
55
50
250
300
350
200
150
100
50
0
EFFI
CIEN
CY (%
)
VIN = 5VBOOST 4 LEDs, 300mAPWM FREQUENCY = 100Hz
EFFICIENCY
LED CURRENT
ISN1ISP1
VIN
IADJ2
IADJ1
FBN
ISP2
FBP
VREF
1MC210µF
C13.3µF
VIN5V
C1: TAIYO YUDEN EMK316BJ335MLC2: TAIYO YUDEN UDK325BJ106MML1: TOKO D53LC (PN# A915AY-2ROM)D1: ZETEX ZLLS1000D2: DIODES INC 1N4148NMOS1: ZETEX 2N7002NMOS2: FAIRCHILD FDG327NLED1 TO LED4: LUMILEDS LXHL-BW02
CC10nF
CSS33nF
300mA
LED1
LED2
LED3
LED4
3477 F07a
75k
6.81k
NMOS1
NMOS2
OUT
100k
0
5V
100Hz
PWM
RC2.4k
RSENSE0.33Ω
SW
L12.0µH D1
D2
SS
GND
LT3477
ISN2
RT
SHDN
VC
Figure 7a. 5V to 4 White LEDs: Boost With PWM Dimming
LT3477
143477fd
For more information www.linear.com/LT3477
applicaTions inForMaTion
Figure 8a. 32V to 6 White LEDs: Buck Mode With PWM Dimming
Figure 8b. PWM Dimming Waveforms
2ms/DIV
ILED500mA/DIV
IL500mA/DIV
PWM5V/DIV
3477 F08b
PVIN = 32V6 LEDs300mA
PWM FREQUENCY = 100HzBUCK MODE
ISN1ISP1
VIN
IADJ2
IADJ1
FBN
ISP2
FBP
VREF
C33.3µF
C12.2µF
VIN3.3V
C1: NIPPON NTS40X5R1H225MC2: TAIYO YUDEN GMK316BJ105MLC3: TAIYO YUDEN LMK316BJ335KLL1: TOKO D53LC (PN# A915AY-100M)D1: ZETEX ZLLS400D2: DIODES INC 1N4148NMOS1, NM0S2: ZETEX 2N7002PMOS: SILICONIX Si2303BDSLED1 TO LED6: LUMILEDS LXHL-BW02
CC0.1µF
CSS33nF
300mA
PMOS
3477 F08a
6.81k
NMOS1
NMOS2
100k
0
5V
100Hz
PWM
280k
10k
SW
D2
SS
GND
LT3477
ISN2
RT
SHDN
VC
RSENSE0.33Ω
PVIN32V
L110µH
LED1
LED6
C21µF
D1
1k 1k
•••
PWM
LT3477
153477fd
For more information www.linear.com/LT3477
applicaTions inForMaTion
Figure 9b. PWM Dimming Waveforms
Figure 9a. 10V to 2 White LEDs: Buck-Boost Mode With PWM Dimming
2ms/DIV
ILED500mA/DIV
IL1A/DIV
PWM10V/DIV
3477 F09b
VIN = 10V2 LEDs300mA
PWM FREQUENCY = 100HzBUCK-BOOST MODE
1M
1k
1k
C210µF
C13.3µF
VIN10V
300mA
49.9k
L14.7µH D1
ISN1ISP1
VIN
IADJ2
IADJ1
FBN
ISP2
FBP
VREF
C1: TAIYO YUDEN LMK316BJ335MLC2: TAIYO YUDEN UDK325BJ106MML1: TOKO D53LC (PN# A915AY-4R7M)D1: ZETEX ZLLS1000D2: DIODES INC 1N4148NMOS1, NMOS2: ZETEX 2N7002PMOS: SILICONIX Si2303BDSLED1, LED2: LUMILEDS LXHL-BW02
CC10nF
CSS33nF
3477 F09a
6.81k
NMOS1
100k
0
5V
100Hz
PWM
SW
D2
SS
GND
LT3477
ISN2
RT
SHDN
VC
RC1.5k
RSENSE0.33Ω
LED2 LED1
PWMNMOS2
PMOS
LT3477
163477fd
For more information www.linear.com/LT3477
Typical applicaTions
800mA, 5V to 12V Boost Converter With Accurate Input Current Limit Efficiency
ISN1ISP1
VINIADJ1IADJ2 ISP2
ISN2
FBN
R3200k
R423.2k
C12.2µF
VIN5V
C310nF
C1: TAIYO YUDEN LMK316BJ225MDC2: AVX 1206YD106MATD1: DIODES INC. B320AL1: TOKO FDV0630-4R7M
C210µF
12V0.8A
3477 TA04a
R217.8k
SW
L14.7µH
R10.033Ω D1
FBP SSGND
LT3477
RT
VC
SHDN
VREF
SHDN
CC4.7nF
RC1k
IOUT (A)0
EFFI
CIEN
CY (%
)
70
75
80
0.4 0.5 0.6 0.7 0.8
3477 TA04b
65
60
500.1 0.2 0.3
55
90
85
5.5V SEPIC Converter With Short-Circuit Protection Efficiency
ISN1ISP1
VINIADJ1IADJ2 FBN
ISP2
R434.8k
R30.15Ω
R10.04Ω
R510k
C13.3µF
VIN3V TO
16V
C433nF
C1: TAIYO YUDEN LMK316BJ335MLC2: TAIYO YUDEN LMK325BJ106MNC3: TAIYO YUDEN LMK316BJ106ZLD1: DIODES INC. DFLS130LL1, L2: TOKO FDV0630-4R7M
C310µF
CC4.7nF
5.5V670mA
3477 TA02a
R218.2k
RC1k
SW
L14.7µH
C210µF
L24.7µH
D1
FBP SSGND
LT3477
ISN2
RT
SHDN
VC
VREF
SHDN
IOUT (A)0
EFFI
CIEN
CY (%
)
85
0.3
3477 TA02b
70
60
0.1 0.2 0.4
55
50
90
80
75
65
0.5 0.6 0.7
VIN = 3V
LT3477
173477fd
For more information www.linear.com/LT3477
Typical applicaTions87% Efficient, 4W LED Driver
ISN1ISP1
VINIADJ1IADJ2
FBN
ISP2
R2200k
C23.3µF
C13.3µF
VIN5V
C333nF
C1: TAIYO YUDEN LMK316BJ335MLC2: TAIYO YUDEN TMK325BJ335MND1: DIODES INC. DFLS120LL1: TOKO A915AY-100M
330mA
LED1
LED2
LED3
LED4
3477 TA03a
R110k
R322k
R60.3Ω
SW
L210µH
R40.05Ω D1
FBP SSGND
LT3477
ISN2
RT
SHDN
VC
VREF
SHDN
CC4.7nF
RC1k
Efficiency
1A Buck Mode High Current LED Driver
Efficiency
IOUT (A)0
EFFI
CIEN
CY (%
)
70
75
80
0.4
3477 TA01b
65
60
500.1 0.2 0.3
55
90
85
ISN1ISP1
VINIADJ1IADJ2
FBN
ISP2
R3280k
R410k
C12.2µF
R10.1Ω
C33.3µF
PVIN32V
VIN3.3V
C433nF
C1: NIPPON UNITED CHEMICON NTS40X5R1H225MC2: TAIYO YUDEN GMK316BJ105MLC3: TAIYO YUDEN LMK316BJ475L1: TOKO A814AY-330MD1: DIODES INC DFLS140
3477 TA05a
R222k
SW
L133µH
1A LEDSTRING C2
1µF
D1
LED4
LED1
•••
FBP SSGND
LT3477
ISN2
RT
SHDN
VC
VREF
SHDN
CC4.7nF
RC1k
LED CURRENT (A)0
EFFI
CIEN
CY (%
)
50
60
70
0.6 1
3477 TA05b
40
30
200.2 0.4 0.8
80
90
100
LT3477
183477fd
For more information www.linear.com/LT3477
Typical applicaTions
ISN1ISP1
VINIADJ1IADJ2
FBN
ISP2
R3200k
R10.1Ω
R410k
C13.3µF
LED BRIGHTNESSCONTROL
0mV TO 650mV
VIN2.7V TO 10V
C333nF
C24.7µF
CC10nF
C1: TAIYO YUDEN LMK316BJ335MLC2: MURATA GRM31CR71E475KA88LD1: DIODES, INC. B320AL1: TOKO FDV0630-4R7M
3477 TA06a
R218k
SW1
L14.7µH D1
LED1
FBP SSGND
LT3477
ISN2
RT
SHDN
VC
VREF
SHDN
LED2
Buck-Boost Mode LED Driver
Efficiency
IOUT (A)0
EFFI
CIEN
CY (%
)
65
70
75
0.6 1.0
3477 TA06b
60
55
500.2 0.4 0.8
80
85
90
VIN = 8V
VIN = 4.2V
VIN (V) IOUT (A)
2.7 0.57 3.6 0.74 4.2 0.83 5 0.93 8 1.0
LT3477
193477fd
For more information www.linear.com/LT3477
pacKage DescripTion
4.00 ±0.10
4.00 ±0.10
NOTE:1. DRAWING IS PROPOSED TO BE MADE A JEDEC PACKAGE OUTLINE MO-220 VARIATION (WGGD-1)—TO BE APPROVED2. DRAWING NOT TO SCALE3. ALL DIMENSIONS ARE IN MILLIMETERS4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.15mm ON ANY SIDE5. EXPOSED PAD SHALL BE SOLDER PLATED6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE
PIN 1TOP MARK(NOTE 6)
0.40 ±0.10
2019
1
2
BOTTOM VIEW—EXPOSED PAD
2.00 REF2.45 ±0.10
0.75 ±0.05 R = 0.115TYP
R = 0.05TYP
0.25 ±0.05
0.50 BSC
0.200 REF
0.00 – 0.05
(UF20) QFN 01-07 REV A
RECOMMENDED SOLDER PAD PITCH AND DIMENSIONSAPPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED
0.70 ±0.05
0.25 ±0.050.50 BSC
2.00 REF 2.45 ±0.05
3.10 ±0.05
4.50 ±0.05
PACKAGE OUTLINE
PIN 1 NOTCHR = 0.20 TYPOR 0.35 × 45°CHAMFER
2.45 ±0.10
2.45 ±0.05
UF Package20-Lead Plastic QFN (4mm × 4mm)
(Reference LTC DWG # 05-08-1710 Rev A)
Please refer to http://www.linear.com/product/LT3477#packaging for the most recent package drawings.
LT3477
203477fd
For more information www.linear.com/LT3477
pacKage DescripTion
FE20 (CB) TSSOP REV L 0117
0.09 – 0.20(.0035 – .0079)
0° – 8°
0.25REF
RECOMMENDED SOLDER PAD LAYOUT
0.50 – 0.75(.020 – .030)
4.30 – 4.50*(.169 – .177)
1 3 4 5 6 7 8 9 10
DETAIL A
DETAIL A IS THE PART OFTHE LEAD FRAME FEATURE
FOR REFERENCE ONLYNO MEASUREMENT PURPOSE
111214 13
6.40 – 6.60*(.252 – .260)
3.86(.152)
2.74(.108)
20 1918 17 16 15
1.20(.047)MAX
0.05 – 0.15(.002 – .006)
0.65(.0256)
BSC0.195 – 0.30
(.0077 – .0118)TYP
2
2.74(.108)
0.45 ±0.05
0.65 BSC
4.50 ±0.10
6.60 ±0.10
1.05 ±0.10
3.86(.152)
MILLIMETERS(INCHES) *DIMENSIONS DO NOT INCLUDE MOLD FLASH. MOLD FLASH
SHALL NOT EXCEED 0.150mm (.006") PER SIDE
NOTE:1. CONTROLLING DIMENSION: MILLIMETERS
2. DIMENSIONS ARE IN
3. DRAWING NOT TO SCALE
SEE NOTE 4
4. RECOMMENDED MINIMUM PCB METAL SIZE FOR EXPOSED PAD ATTACHMENT
6.40(.252)BSC
FE Package20-Lead Plastic TSSOP (4.4mm)
(Reference LTC DWG # 05-08-1663 Rev L)Exposed Pad Variation CB
DETAIL A
0.60(.024)REF0.28
(.011)REF
Please refer to http://www.linear.com/product/LT3477#packaging for the most recent package drawings.
LT3477
213477fd
For more information www.linear.com/LT3477
Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representa-tion that the interconnection of its circuits as described herein will not infringe on existing patent rights.
revision hisToryREV DATE DESCRIPTION PAGE NUMBER
D 03/17 Clarified efficiency in DescriptionClarified VREF in Block Diagram
16
(Revision history begins at Rev D)
LT3477
223477fd
For more information www.linear.com/LT3477
Linear Technology Corporation1630 McCarthy Blvd., Milpitas, CA 95035-7417
LINEAR TECHNOLOGY CORPORATION 2005
LT 0317 REV D • PRINTED IN USA
(408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com/LT3477
relaTeD parTs
Typical applicaTion
PART NUMBER DESCRIPTION COMMENTS
LT1618 Constant Current, Constant Voltage 1.4MHz, High Efficiency Boost Regulator
VIN: 1.6V to 18V, VOUT(MAX) = 5.5V, IQ = 2.5mA, ISD < 1µA, QFN16 Package
LT3436 3A (ISW), 800kHz, 34V Step-Up DC/DC Converter VIN: 3V to 25V, VOUT(MAX) = 34V, IQ = 0.9mA, ISD < 6µA, TSSOP16E Package
LTC®3453 Synchronous Buck-Boost High Power White LED Driver
VIN: 2.7V to 5.5V, VOUT(MAX) = 5.5V, IQ = 2.5mA, ISD < 1µA, QFN16 Package
LT3466 Dual Constant Current, 2MHz, High Efficiency White LED Boost Regulator With Integrated Schottky Diode
VIN: 2.7V to 24V, VOUT(MAX) = 40V, IQ = 5mA, ISD < 16µA, DFN Package
LT3479 3A, 42V Full Featured Boost/Inverter Converter With Soft-Start
VIN: 2.5V to 24V, VOUT(MAX) = 40V, IQ = 5mA, ISD < 1µA, DFN/TSSOP Packages
LTC3490 Single Cell 350mA, 1.3MHz LED Driver VIN: 1V to 3.2V, VOUT(MAX) = 4.7V, ISD < 1µA, DFN/SO8 Packages
Buck Mode High Current LED Driver
Efficiency
LED CURRENT (A)0
EFFI
CIEN
CY (%
)
50
60
70
0.6 1
3477 TA05b
40
30
200.2 0.4 0.8
80
90
100
ISN1ISP1
VINIADJ1IADJ2
FBN
ISP2
R3280k
R410k
C12.2µF
R10.1Ω
C33.3µF
PVIN32V
VIN3.3V
C433nF
C1: NIPPON UNITED CHEMICON NTS40X5R1H225MC2: TAIYO YUDEN GMK316BJ105MLC3: TAIYO YUDEN LMK316BJ475L1: TOKO A814AY-330MD1: DIODES INC DFLS140
CC4.7nF
3477 TA07
R222k
RC1k
SW
L133µH
1A LEDSTRING C2
1µF
D1
LED4
LED1
•••
FBP SSGND
LT3477
ISN2
RT
SHDN
VC
VREF
SHDN