14 year hrl research
TRANSCRIPT
IBM Labs in Haifa © 2008 IBM Corporation
Riding on Maxwell Equations14 years of Analog Fun !
David Goren
IBM Labs in Haifa
© 2008 IBM Corporation2
The starting point (1998)The starting point (1998)Ringing noise example -"Phoenix" projectRinging noise example -"Phoenix" project(SiGe Pin Electronics Driver/Receiver)(SiGe Pin Electronics Driver/Receiver)
Example:
1 [mm] on-chip interconnect = 6.7 [psec] time of flightOutput wire electrical parameters
R=2.5 C=70fF (from cap. extraction, equiv. to 1um HBT)L=0.6 nH (estimated as Linfinity from the capacitance)Swing = I25 Ohm = 0.5 VoltMax. overshoot: L dI/dt = 0.24 Volt !
Interconnect
Driver (Phoenix project)25 500 fF
Driver output: 20mA switching in 50psec into 25 Ohm load
D. Goren et al, IEEE BIPOLAR/BICMOS circuits and technology meeting, Minneapolis, September (1999).
IBM Labs in Haifa
© 2008 IBM Corporation3
Simulated result Simulated result (model estimated inductance) (model estimated inductance)
25% overshoot ! (spec. requires 5%)
no inductance
inductance included
Just imagine this interconnect line in sensitive comparatorinput ! !
IBM Labs in Haifa
© 2008 IBM Corporation4
Problem definition:Silicon chip metal interconnect
design & modeling methodologiesfail at high frequencies
Chip level extraction is not the right way at high frequencies: State of the art in interconnect extraction is mostly RC. Even
around 1GHz, inductance starts to impact longer lines behavior Fully automated inductance extraction is impossible without
exact knowledge of the return paths, which is not always practical at post layout extraction
Post layout extraction for high frequency design is often too late Traditional microwave methodology does not apply to VLSI and
A&MS Traditional microwave concepts (Impedance matching, S -
Matrix) are not applicable for most A&MS designs Fully nonlinear, large signal transient SPICE simulations
required Mixed signal simulations required
IBM Labs in Haifa
© 2008 IBM Corporation5
Our unique solution:Global wires can be designed as
independent, stand-alone devicesInterconnect Design rather than extraction -
Combine design automation with designer’s wisdom
Study and implement the closed environment conditionsenabling stand-alone devices for critical wire structures
Use predefined T-line geometries as design templates Properly designed bends and junctions not requiring separate
models – except few cases in mm-Wave design Develop closed form, wide bandwidth (DC till the transistor Ft)
models for the given geometries (over 200GHz bandwidth today) Support the specific technology details (given metal stack, various
dielectric materials, copper..) Support all simulation kinds (transient, AC, PSS, S-param, mixed-
mode Easy migration between different circuit simulators and design
environments (VerilogA based models)
Vision: From IBM standard upgrade to an industry standard
IBM Labs in Haifa
© 2008 IBM Corporation6
Optimalgeometry
Semi-analyticalmodeling
EquivalentRLC network
Our approach: We suggest self-contained models for carefully designed T-lines only Focused on careful design of on-chip critical wiring which ensures both
desired performance and modeling accuracy in various/dense VLSI design neighborhoods
Required modification and expanding of the model is enabled by physics-based semi-analytical explicit expressions for the RLC network elements
On-Chip T-line Methodology
Previous solutions: focused on modeling on-chip wiring for circuits which had been considered
as given. They had tried to model any critical wiring in any given design
IBM Labs in Haifa
© 2008 IBM Corporation7
Microstrip T-lines: up to 110 GHz, for relatively sparse A&MS SiGe design
S
G
S2S1
G
GG S
G
via
via
GG S2S1
G
via
via
On-Chip Interconnect Design Suite:Till 2002
Do not consider the T-line device neighborhood
Consider dielectric as uniform medium
Towards 2002, the microstrip T-lines were already available in almost all SiGe Foundry Design Kits and won numerous customers.
This resulted in an IBM Research Accomplishment Award in 2002.
IBM Labs in Haifa
© 2008 IBM Corporation8
First T-lines Test Cage (BiCMOS7HP)
Haifa on-chip microstrip straight and bent T-line structures
IBM Labs in Haifa
© 2008 IBM Corporation9
Measured S-parameters of bent T-line structures versus their straight reference
Dashed: 45o bends, dotted: 90o bends, solid: straight line
S11(magnitude) S11(phase)
S12(phase)S12(magnitude)
Sample Measurement Results
IBM Labs in Haifa
© 2008 IBM Corporation10
S
G
Dirac BiCMOS8HP Test Cage
Haifa on-chip microstrip T-line structures
IBM Labs in Haifa
© 2008 IBM Corporation11
Green: model Blue: 110 GHz measurement, Black: EM solvers Red: raw measurement (no pad de-embedding)
Thomas Zwick, Youri Tretiakov and David Goren, IEEE Microwave and Wireless Components Letters (2004)
Sample Dirac Measurement Results: Single Microstrip T-line
IBM Labs in Haifa
© 2008 IBM Corporation12
Integration Level 359 NPNs 1040 FETs 157 transmission
lines 13 inductors 521 resistors 270 MIMs 60 pads
Size: 4 x 1.5 mm2
Driver
PLL
Mixer & IFVGA
TriplerIF Mix
PA
High integration level is unique for millimeter-wave.
Complexity approaching that seen at 5 GHz.
Die Photo: A 60-GHz Transmitter(taken from the talk at the ’06 IBM BEOL Conf.
made by Brian Gaucher’s team)
IBM Labs in Haifa
© 2008 IBM Corporation13
60 GHz SiGe Transformer Based Power Amplifier
Combine the power of 4amplifiers (add 6dB!)
Voltage swing well above transistorbreakdown voltage
Efficient impedance matching Compact design Extremely compact design Single-ended or differential operation
possible (balun)
IBM Labs in Haifa
© 2008 IBM Corporation14
Measured Performance:
23 dBm (200mW) RF power at 60GHz (world record for Silicon)
Up to ±6.5V voltage swing in 100Ω (BVceo = 1.7V)
20 dB gain (two stage) Wilkinson power divider used to
distribute input power Extremely compact design Can be used for input impedance
transformation too
4:1 TransformerSize: 1.8 x 2 mm2
Wilkinson Power Divider
60 GHz SiGe Transformer Based Power Amplifier
Ullrich R. Pfeiffer and David Goren, IEEE Journal of Solid State Circuits, 2007
IBM Labs in Haifa
© 2008 IBM Corporation15
Variable T-lines
R1 S R1
sC port lines
ws w
ground
R2Rn R2 Rn
crossingcrossing
New concept: maximal flexibility hardware independently controlled by software
IBM Labs in Haifa
© 2008 IBM Corporation16
Variable T-lines – top view
SR2 R1
IBM Labs in Haifa
© 2008 IBM Corporation17
3D EM simulation(IBM varsinglewire device)
C port lines
IBM Labs in Haifa
© 2008 IBM Corporation18
IBM varsinglewire device: user interface
IBM Labs in Haifa
© 2008 IBM Corporation19
IBM varsinglewire device: S-parameter simulation
We use Cadence vector wire (bus) for elegantly implementing the C ports
Alternating floating and grounded ports case
IBM Labs in Haifa
© 2008 IBM Corporation20
Simulation Results, 50, 360um Variable T-line
19% extra delay
All C port lines open
All C port lines shorted
At 60GHz, the impedance of the varsinglewire device is:All C ports floating 48.5 OhmAll C ports grounded 40.4 Ohm
IBM Labs in Haifa
© 2008 IBM Corporation21
Microstrip T-lines: Up to 200 GHz, mostly for SiGe RF & mm wave customers
S
G
optionalcrossunder
optional cossover
S2S1
Goptional crossunder
optional crossover
GG S
G
via
via
optional crossover
optional crossunderGG S2S1
G
via
via
optional crossover
optional crossunder
GG S
Silicon substrate
GG S2S1
Silicon substrateoptional crossunder
optional crossover
optional crossunder
optional crossover
Coplanar T-lines: Up to 100GHz, mostly for Digital CMOS, includes silicon effects
RC Lines: Digital CMOS: short wires/lower frequencies
X2X1 S GG S2S1
crossunder
crossover
crossunder
crossover
IBM On-Chip Interconnect Basic Design Suite:Ever Since 2003
Introduced modeling of:
Crossing lines
Silicon substrate
Non-uniform dielectric structure (low-k)
Metal fill
Copper layers properties (cheezing, OPC etc.)
Towards 2007, the breakthrough to mainstream CMOS technologies. This resulted in an IBM Research Upgrade to Outstanding Accomplishment
Award in 2007.
IBM Labs in Haifa
© 2008 IBM Corporation22
GG S
Silicon substrate
crossunder
crossover
Y2
X1 X2
Y1
w s wT-line
core structure
The T-line Closed Environment Concept
T-line closed environment – a design fragment
which can be accurately represented by a self-contained, independent model
of the T-line core structure in an actual design environment
T-line closed environment = T-line core structure + ?
ConclusionsSelf-contained models for critical lines in dense
VLSI Manhattan environments are possible in most common cases, provided that
the critical lines are properly designed – proper design guidelines are suggested
the models are modified and expanded to include some environment elements, such as:
silicon substrate, crossing lines, correction of the DC resistance due to the power grid impact
Closed Environment = Proper Design + Proper Modeling
IBM Labs in Haifa
© 2008 IBM Corporation23
Impact of 3D Crossing Lines
G S G
Impact of crossings on T-line Capacitance:
C = C(hover/under, wover/under, Dover/under)
soverwover
hover
hunder
sunder
wunderT-line
Crossover
Crossunder
tover
tunder
t
D
C
0 100%
C(full plane)
C(no crossings)D = w/(s+w) is crossing metal density
IBM Labs in Haifa
© 2008 IBM Corporation24
signal
ground
Metal+via fill
signal
Metal fill
Metal fill
ground
Via fill
Metal fillVia fill
Metal fillVia fill
…
3D Metal and Via Fill Study
Conclusions1) Metal fill can be tolerated and estimated by the T-line model, but via fill should better be avoided or excluded from the vicinity of the T-lines2) It is recommended to reduce the process metal fill density in the vicinity of the T-lines to less than 15%
IBM Labs in Haifa
© 2008 IBM Corporation25
Randall CMOS11S0 Test Cage
Haifa coplanar T-lines test cage - Loki design structures
IBM Labs in Haifa
© 2008 IBM Corporation26
Single CPW, no crossing lines, w=s=2um (gamma, z0)
Green & Magenta: 60GHz measurement on two different chips Cyan: Haifa T-line model Black: EM solvers Blue: RC model
Sample Randall Measurement Results
IBM Labs in Haifa
© 2008 IBM Corporation27
Pathfinder CMOS12LP Test Cage
Haifa coplanar T-lines test cage – CPW T-line structures
IBM Labs in Haifa
© 2008 IBM Corporation28
Sorting wires into 2 groups: critical, small group non-critical, most of the wires
Design of critical wires: Predefined set of parametrized T-line
structures as design components Pcell based: T-line device =
symbol+schematic+layout views DRC and LVS clean layout Monitoring T-line parameters is
enabled
Smart extraction Use T-line models for critical wires Use RC extract for non-critical wiring -
sufficient accuracy Back-annotate final T-lines
parameters
Schematic design including T-line models
Smart Extraction
Physical Design. T-lines as p-cells
Final Simulation
High Level Design
FloorplanArchitecture
Identify critical interconnect
Patented Interconnect-aware Design Flow
D. Goren et al, IEEE DATE conference, Paris (2002). D. Goren et al, IEEE DAC conference, Anaheim (2003).
David Goren et al, Patent Number 10/091,934 filed on March 6 (2002).
IBM Labs in Haifa
© 2008 IBM Corporation29
RC Extraction Models
Models Verification by Comparison to Other Models
IDENTIFY CRITICAL PATHi.e. High Speed Clock Path
HIGH LEVEL DESIGNFloorplan, Architecture
GEOMETRY OPTIMIZATION USING RC
or CPW MODELS Corners and Monte Carlo
can be run
OPTIMAL GEOMETRYi.e. High Speed Clock
Path
CPW or RC Models From
Haifa TLine Team
CIRCUITS DESIGN AND SIMULATIONS WITH RC AND CPW MODELS
Corners & Monte Carlo
GeometryOptimization
Design RequirementsNot Met
CIRCUITS EXTRACTION AND SIMULATIONS
M2 P M2 N
SUBSTRATE
M4 Crossing (VDD): Width=0.2um, Spacing=0.2um, Thickness=0.25um
0.72um 0.72um 0.72umw=0.96umw=0.96um
w=0.96um
M2w=0.96um
Th=0.74u
Th=0.25um
11G Squall Clock Lines Cross-section, L=400um
High level and high speed clock distribution design flow
Nominal 3-Db bandwidth, 25fF Load C 100 Ohms source imp. 9fF Diffusion
13.7GHz Haifa RC 14.4GHz Haifa CPW 13.8GHz Erie RC
Haifa Coplanar Waveguide and RC models in HSS environment
(from the talk at IBM BEOL’06 Conf. made by H. Camara, HSS team)
IBM Labs in Haifa
© 2008 IBM Corporation30
Waternoose 2.7 GHz Clock Tree Loki 2.7 GHz Clock Tree
• Loki needed far fewer clock buffers to preserve clock amplitude using Haifa T-Lines.
• Easy to balance skew with a passive tree.
• Some clock paths are a passive multi-drop branch
RC-Lines (Waternoose) vs T-lines (Loki)(taken from the talk at the ’06 IBM Academy Analog Conf.
made by HSS team)
IBM Labs in Haifa
© 2008 IBM Corporation31
Loki environment: Coplanar T-line vs. RC-line example
GG Scrossunder
1 mm wire
IBM Labs in Haifa
© 2008 IBM Corporation32
Simulation experiment results: Coplanar T-line vs. RC-line – far end (length=1mm)
trise =10ps
trise = 28psT=370ps
IBM Labs in Haifa
© 2008 IBM Corporation33
Contribution to IBM Foundry DK’s, 2001-2011
Integration of the Haifa Interconnect Design Suite in IBM Design Kits Till 2002, almost all the SiGe technologiesSince 2002, all the SiGe technologies + the following CMOS technologies:
CMRF8SF, CMOS9SF, CMOS9FLP, CMOS10LP, CMOS10SF, CSG11S0, CMOS11LP, SOI12S0, SOI13S0, 22nm SOI
Since 2007, transition of the coplanar T-line and RC-line models to VerilogA VerilogA based models require significantly less integration effort from the BTV design automation team, enable standard integration in various EDA environments
VerilogA based models are already in the IBM DK’s for the following technologies: CMS9FLP, CMOS10SF, CMOS11LP, SOI13S0, 22nm SOI
Introducing new devices to the Haifa Interconnect Design Suite 2008, R&D of generic compact BUS models and RC-BUS models towards "T-line style" BUS
devices – delivered to BTV – need more internal customer blessing for kit integration
2011, 3DI TSV / mC4 models will be integral part of IBM 22nm design kits.Annual customer satisfaction surveys – feedback from BTV:
“Very satisfied with excellent quality product”
IBM Labs in Haifa
© 2008 IBM Corporation34
Wires parallel to the T-line have almost no impact on T-line capacitance Impact on T-line inductance
Significant inductive impact may be caused by parallel lines located in layers adjacent to the T-line core structure layer, right above crossover and/or right below crossunder
The inductive impact strongly depends on the horizontal shift of parallel lines relative to the signal line
The inductive impact of parallel lines is pronounced at higher frequencies.
The preliminary study considers parallel wires having periodic structure, i.e. characterized by constant wires width and spacing
Future idea: Impact of Parallel Lines on T-line performance:to be included in future design kits
G S G
Crossover
T-line core structure
Parallel lines above
Crossunder
Parallel lines below
Silicon substrate
IBM Labs in Haifa
© 2008 IBM Corporation35
BUS device and model templates enable easy high speed BUS design and modeling in the pre-layout stage by the average designer, who is not an electro-magnetic expert
Who needs this? P7 and other processor designs,HSS core designs, RFIC designs (BUS design can bethe bottleneck for multi-GHz speed)
Other usage example: Accurate inductive (and capacitive) crosstalk estimation (Ericsson case, for example)
RC compact multi-line models are included for lower frequencies
Future Impact: Compact Bus Models
IBM Labs in Haifa
© 2008 IBM Corporation36
Future Impact: Compact Bus Device
G S2S1 Sn
Crossover
Bus core structure
Parallel lines above
Crossunder
Parallel lines below
Silicon substrate
•Distributed bus model, including full inductance matrix for all the signal lines S1-Sn, considering crossing and parallel lines in relevant adjacent levels •Includes skin effect (frequency dependence) modeling
G
Model window
IBM Labs in Haifa
© 2008 IBM Corporation37
5 Signal Lines: CPW vs. RC vs. EM Solver, 11000 mode, gamma-Z0 format stack: 323102, signal in UB, crossing in UA, parallel in E1, w=s=2um, d=3um
1mm lines, simulation from 10[MHz] up to 50[GHz]
Sample Simulated Results
IBM Labs in Haifa
© 2008 IBM Corporation38
Simulation Result (1.6mm length)Center signal excited, the rest is off
1 2 3 4 5G G
IBM Labs in Haifa
© 2008 IBM Corporation39 1 2 3 2 1G G
zGryphon Bus Simulated Result (1.6mm length)Signals 1 2 3 have same phase (not design practice)
IBM Labs in Haifa
© 2008 IBM Corporation40
Interconnect for 3DI:design and modeling motivation/challenges
Target Provide means to design in 3DI technologies considering vertical, as
well as horizontal, interconnect which enable precise prediction of expected circuit behavior – current focus on z360 design in 22nm
Required solution features Should provide high broadband accuracy for both A&MS and digital
design (at least from DC up to 3rd signal harmonic) in actual design environment, including silicon substrate, surrounding vertical and horizontal interconnect, etc.
Designer friendly does not require a deep electromagnetic understanding “protects the designer against himself” supports the given specific technology details (given metal stack,
dielectric structure etc.) simple and very fast in operation
Fully integrated within common design flows (e.g., Cadence, CTE) Supports all simulation kinds: transient, AC, S-Parameters, PSS
IBM Labs in Haifa
© 2008 IBM Corporation41
The Vertical T-line Concept
metal
Oxide Silicon
S GG
Properly shielded, predefined T-line designs are the key for bothcritical horizontal and vertical wires in any IBM silicon chip technology
The 10 year Haifa T-line design and modeling expertise as the core IP Planned to be fully integrated within future BTV 3DI design kits as T-
line style devices We target standard best design practice vertical structures, thereby
both improving the performance and simplifying the modeling
TSV T S T-line
IBM Labs in Haifa
© 2008 IBM Corporation42
The silicon dielectric relaxation effectfirst discussed during my 2008 visit to YKT
G
Grounded silicon
SGoxide
IBM Labs in Haifa
© 2008 IBM Corporation43
TSV + small C4 combinationESCHER& z360
S0
SP
G GS G GS
Face to back and face to face combinations are possible in principle
IBM Labs in Haifa
© 2008 IBM Corporation44
TSV connection to C4:Vertical model domain
RB
RA
YF
WIWJ
WK
6.86
Array DT Moat
DTp-
n+
50
4
1.0 ?
5.61
2.612.0
3.0
1.0
TSV model domain
TSVV
N+ Epi SOI Target Dopant Profile
1.0E+12
1.0E+13
1.0E+14
1.0E+15
1.0E+16
1.0E+17
1.0E+18
1.0E+19
1.0E+20
0 1 2 3 4 5 6 7 8
Depth (um)
Phos
(at/c
m3)
To package
22SOI 3DI DM,
Sep 2010
z360 (22nm)
IBM Labs in Haifa
© 2008 IBM Corporation45
“4-on-7” C4 Pattern (typical)
gnd
vdd vcs
S S S S S
S S S S S
185.618
5.6
vdd vdd vddvcs vcs
gndgndgndgndgndgnd
gnd gnd gnd gnd gnd gndgnd
Signal TSV to be modeled
12
TSV connection to C4:Horizontal model domain
TSV corner parameter [-1 ..1] Considers the 1 and 2 neighbor TSVs impactCorner = -1: neighbors bear “hostile” signals Corner = 0: neighbors are ground/VDD Corner = 1: neighbors bear “friendly” signals
371.2
z360 (22nm)
IBM Labs in Haifa
© 2008 IBM Corporation46
TSV pattern – problem definition
gnd
1
2
gnd
gnd
gnd
gnd
gnd
S
z360 (22nm)
IBM Labs in Haifa
© 2008 IBM Corporation47
TSV model user interface
Delivered to 3DI team on Nov 30 2010
z360 (22nm)
IBM Labs in Haifa
© 2008 IBM Corporation48
TSV model results: S-parameters up to 60GHz z360 (22nm)
IBM Labs in Haifa
© 2008 IBM Corporation49
Mini-C4 connection between 2 strata for z360:horizontal model domain
Signal Mini-C4 to be modeled
gnd1
2
34
5
6
gnd
gnd
1
2
34
5
6
gnd
Mini-C4 corner parameter [-1 ..1] Considers the 1- 6 neighbor mini-C4’s impactCorner = -1: neighbors bear “hostile” signals Corner = 0: neighbors are ground/VDD Corner = 1: neighbors bear “friendly” signals
RB wiring connected to GND mini-C4s
z360 (22nm)
IBM Labs in Haifa
© 2008 IBM Corporation50
Mini-C4 connection between 2 strata:RB wiring impact in case of grounded neighbors and RB wiring
mini-c4 capacitance to grounded neighbors:impact of the gap between pads and GND wires
55.0
60.0
65.0
70.0
75.0
80.0
85.0
0 10 20 30 40 50 60 70
gap, um
C, f
F
RB power grid removed: C = 24 fFOnly wires close to pads removed: C = 33 fF
gap = 1.2um =min DRC
70
1.2
z360 (22nm)
IBM Labs in Haifa
© 2008 IBM Corporation51
Mini-C4 model user interface
Corner factor
Delivered to 3DI team on Nov 9 2010
z360 (22nm)
IBM Labs in Haifa
© 2008 IBM Corporation52
Mini-C4 model results: S-parameters up to 50GHz
Proper shielding in RB level reduces crosstalk between mini-C4s
z360 (22nm)
IBM Labs in Haifa
© 2008 IBM Corporation53
Target:Design and develop compact models for metal on-chipinterconnect at THz frequencies in existing silicon technologies
Exploratory Research:Explore the boundary between electronics and photonics
• What are the fundamental physical limitations for using metal wires, as opposed to dielectric fiber optics, as on-chip interconnect at ultra high frequencies?
• How to design such ultra high frequency T-lines on-chip?
• How to model these T-lines?
Why do we think it will be successful:We have a proven expertise in the design and compact modeling of broadband on-chip metal interconnect, confirmed by hardware measurements from DC till 110GHz, and used extensively in IBMYKT 60GHz wireless designs.
THz On-Chip: THz level T-line Devices
IBM Labs in Haifa
© 2008 IBM Corporation54
Surveillancemedical
• 94GHz and 120GHz Radar and imaging applications exist today, which require modeling up to the 3rd harmonic (~360GHz)• THz transistors are becoming reality: Ft =400GHz for SiGe (500GHz nitrogen cooled), 660GHz for InP, etc. • THz frequencies are considered for security surveillance and medical imaging applications:• New idea: THz fiber communication !
THz level on-chip metal interconnects will be needed
THz On-Chip: THz level T-line Applications
IBM Labs in Haifa
© 2008 IBM Corporation55
Early feasibility study in Haifa shows that: Our electromagnetic analytical T-line modeling approach can be in
principle upgraded to the THz regime – including a complete DC to THz bandwidth modeling.
HFSS verification of the T-line models can be used up to 1THz as first step. Some EM verifications up to 400GHz of our single microstrip T-line have already been performed.
Calculations show that specific copper T-line structures can perform well at 1 [THz]
Fundamental physical effects up to 10THz are being studied in Haifa:- Nonlinear metal scattering effects (Drude model) starts beyond several THz and can be formulated and included in the model- THz effects in semiconductors are under study
Potential collaboration: wuppertal university (Germany): (Ullrich Pfeiffer, a former IBMer) for
performing measurements up to 4 THz (amplitude only).
THz Bandwidth T-line Devices – current progress
IBM Labs in Haifa
© 2008 IBM Corporation56
When the period of the radiation becomes comparable to the mean time between collisions in the metal (relaxation time), we get that:
The metal conductivity δ starts to decrease, becoming inversely proportional to the frequency
The skin depth δ stops to be frequency dependent, and saturates
The T-line resistance per unit length R starts to grow in proportion to the frequency (no more to the square root of the frequency) till the losses become excessively high
THz Bandwidth T-line DevicesThe Skin Depth Saturation Effect
f
σDC
f
δsat
Fc f
Log(R)
RDC
Log(δ)
Fc FcFtr
√f
f1 / √fConst.
1 / f
Log(σ)
00
2
π21Fc m
nq nm
qsat 021
250)(
6)(
Cusat
THzCuFc
IBM Labs in Haifa
© 2008 IBM Corporation57
TeraMos Research Background Research Collaboration between IBM and Technion -
Israel Institute of Technology Research Proposal to European Community: FET OPEN
not accepted – now applying for another one IBM FACULTY AWARD 2008 )Y. Nemirovsky, Technion -
Israel Institute of Technology, promoted by David Goren) TMOS (CMOS-SOI-MEMS) transistor for uncooled IR
Imaging, published IEEE Trans. On Electron Devices, Nemirovsky Group, Technion
TMOS Technion patent application (2003) TeraMos Technion provisional patent application
(2008) IBM Antenna Coupled THz sensor patent (2010) HRL No. 1 FRR project.
IBM Labs in Haifa
© 2008 IBM Corporation58
TeraMOS - THz FPA Imaging silicon chip with MEMS post processing
IBM patent FILEDcapacitively coupled antenna conceptImproves performance dramatically
IBM innovative on-chip antenna design
Suspended diode / transistor by MEMS
Technion Patented Technology
2D FPA testsite in IBM CSOI7RF – back in Haifa
Firm calculations show NEP ~ 1 pW/√Hz – Passive THz Imaging in Silicon!
IBM Labs in Haifa
© 2008 IBM Corporation59
Operation Principle of Thermal Sensors
Simplified modeling assumes a thermal mass capacitance C connected to a heat sink at T0 through a total thermal conductance G which absorbs the radiation power P with efficiency
d TC G T Pdt
2
/0
1 2
( ) (1 )t
P f GT f
CfG
PT t eG
Steady State:
Thermal Time Constant: CG
0PTG
Heat Balance eq.
Heating Transient:
IBM Labs in Haifa
© 2008 IBM Corporation60
The patented TMOS / TeraMOS Detector
The sensing element is a MOS transistor operating in sub-threshold The current mechanism is diffusion and is therefore very sensitive to temp. The enabling technology is any standard CMOS-SOI process (IBM is excellent) Sensor matrix is fabricated first, followed by micromachining post-processing
which can be done at the Technion or any advanced MEMS facility Measured sensitivity of TMOS ~ 4% (better than standard Honeywell
bolometers) - achievable NETD < 30mK for IR imaging (8-14um) The TeraMOS detectors are made of large multi-finger transistors on the larger
THz pixel dimensions (200um x 200um)
IBM Labs in Haifa
© 2008 IBM Corporation61
Transistor
holding arm: electrical wires &thermal isolation
Thermally Isolated Transistor as “active Bolometer”
Taking the THz Bolometer Concept to its feasible limit
IBM Labs in Haifa
© 2008 IBM Corporation62
MOS transistor operating in the sub-threshold region
VDD
Vg
Id
2 2
*2
2
1 1
1 1 ( )
GS T
DS BB
V Vq
qV k Tnk TBDS ox
TGS T
k TWI C n e eL q
dVdI q qTCC V VI dT T nkT nkT dT
Exponential Current Temperature DependenceLarger TCC at deeper subthreshold Low Power Consumption Low self heating (no need for pulsed operation)
E. Socher, S. M. Beer, Y. Nemirovsky, "Temperature Sensitivity of SOI-CMOSTransistors for Use in Uncooled Thermal Sensing", IEEE Trans. On ElectronDevices, IEEE Trans. On Electron Devices, 52(12), 2784-2790 (2005)
The active bolometer
IBM Labs in Haifa
© 2008 IBM Corporation63
TeraMOS MEMS Fabrication in the Technion: Built-in Al Masks provided by CMOS
- Active
- Poly
- Met1
- Met2
- Met3
- ILD
- BOX
- Wafer
(a) (c)(b) (d)
CMOS-SOI Wafer Fabrication in any Standard FAB – such as IBM Back Side DRIE Anisotropic Etching of Silicon,
BOX provides etch stop Front Side RIE Etching of ILD using CHF3;
flourine plasma does not etch Al Masks Front Side Metal Mask Etching
IEEE Trans. On Electron Devices (2009)
IBM Labs in Haifa
© 2008 IBM Corporation64
Measured noise current PSD (Technion)of "virgin" & TMOS transistors at 30Hz
from deep subthreshold to saturation.
10-10
10-8
10-6
10-4
10-28
10-26
10-24
10-22
10-20
Drain Current (A)
Pow
er S
pect
ral D
ensi
ty (
A2 /H
z)
P43 VirginP43 TMOSP68 VirginP68 TMOS
Estimatedoperation
current
Releasing increases a bit the 1/f noise
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IR Electro-optical Characterization:Experiment set up in the Technion
• Detector is electrically biased for correct operation point
• Black Body radiates IR radiation (power level depends on temp.)
• Chopper is used to lock the signal in lock-in amplifier
• Output is measured vs. chopper frequency
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Signal vs. chopper frequency:Excellent fit of measurement to theory
2)2(1
1)(**)(
GCf
GfPITCCfSignal
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The Antenna Coupled TeraMOS (IBM Patented)
Includes high bandwidth back-reflector on a separate chipActual antenna type may differ from this one
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300 um
Antenna
AntennaAntenna
Platform
~20um
IBM TeraMOS Pixel Design
Arm length designed for G=1.6x10-8 Watt/°K
Proper mechanical design of holding arm is critical to minimize platform deflections !
Fill Exclude around the antenna (from all metals and poly and RX as well) is crucial to maintain proper antenna performance!
Metal densities
Are far exceeded
in this design (AM
And MT)
It is crucial to design the bending of the holding arm to minimize any horizontal and vertical displacements of the platform !
This is the main bottleneck of this whole design.
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Preliminary Layout – Full Matrix
0.2um RIE shielding
0.5um RIE shielding 0.1um RIE shielding
1um RIE shielding
Orange square is DRIE hole. We have 4 X (2 X 2) pixels. Each quarter will contain 2 diodes and 2 NMOS
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TeraMos System Design Goals
Topic TeraMOS Design Goals
New System Compact Passive Staring FPA (0.6-1.5THz); for stand-off ranges of ~10-50 meter and real-time passive imaging.High Performance (NETD <1K);Low Cost (<$10000). Image: metallic, ceramic or plastic objects (security - people screening)tissue, tumours, teeth (medical – skin cancer detection, dental)
New TeraMOS Sensor
low NEP- Noise Equivalent Power – 1pWatt/ Hz1/2;Low NETD- Noise Equivalent Temp. Difference-<1K. Oper. Temp.: 77K (a good compromise between noise reduction and added system cost). Stirling cooler ~ $4000, MTTF: 15,000 hours)
New FPA architecture
High bandwidth of operating frequency: 0.6-1.5THz. Low Freq.- 0.6THz: optimized to wavelength penetrating clothing;High Freq.- 1.5THz: optimized for spatial resolution
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Backup Slides
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Standard CMOS-SOI TechnologyStandard Bulk Micromachining and Built-In MasksActive bolometer – MOS transistor at sub-thresholdLow current eliminates self heatingOn-Chip High resolution THz Focal Plane ArrayOn-chip integrated analog readout in standard CMOSPotential passive THz imaging at room temperaturePotential massive deployment for low cost passive
THzremote imaging at any crowded place
Medical applicationsJust applied to a European fund project (FP7)
Summary – TeraMOS Advantages
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Early 2008 beginning –“TSV first” processTSV first
a) ~1.2 um, landing pad
b) ~12-13 um TSV post though Si and m1-c1 BEOL
c) ~10 um TSV though c2-ub+ BEOL
d) ~1-2 um post key
e) ~22-23 um
a
c
b
d
e
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2008 – 2009 beginning –TSV / MSV pair connection
MSVTSV
TSV/MSV pair Black Box boundary
TSV / MSV pair
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TSV/MSV pair within the dense via farm: modeling approach
TSV/MSV pair to be modeled
TSV / MSV pair
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TSV/MSV pair model: Cadence S-parameters simulationTSV / MSV pair
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TSV/MSV pair model RLCG simulation up to 40Ghz, nominal (corner factor=0)TSV / MSV pair
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TSV Model:Example
Modeled element
Lumped Model
Lumped model: built from s-parameter data; in use for short-reach, long-reach I/O analysis
Parameterized models have been built to support technology definition exploration
Model-hardware correlation structures and test plan in place (Escher technology sites)
Depth: 70
All units: m
large low frequency cap:
key issue for I/O
Example result: EM solver vs. modeled TSV capacitance characteristic
From Status Update for Milestone“Complete Interconnect Compact Model Delivery, I/O
Circuit Design, and Design for Test Plan for 3D Test Vehicle”
by D. Friedman, YKT, Jan 2009
TUNGSTEN TSV
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Cadence S-parameters simulation example(Tungsten TSV symbol shown)
TUNGSTEN TSV
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4 bar tungsten TSV EM solver and Haifa model resultsexpressed as RLCG(f) up to 50GHz
TUNGSTEN TSV
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Investigating 3D I/O Demands TSV, mC4 Modeling Key I/O questions to be addressed by Escher work
Performance of long reach links (where the TSV is an added impairment for a backplane link) Performance/power requirements for short reach links (those connecting layers within a 3D stack)
S1
S0
S2
[Note: modeling work can also be leveraged to predict through-via performance of alternate technology approaches and for Si carrier through-via analysis]
Key elements to be modeled Inter-layer elements
Single signal-carrying C4 in various environments
Single set of signal-carrying W TSV bars in various environments
Stack escape elements Group of signal-carrying W TSV bars
in a C4 unit cell in various environments
From Status Update for Milestone“Complete Interconnect Compact Model Delivery,
I/O Circuit Design, and Design for Test Plan for 3D Test Vehicle”
by D. Friedman, YKT, Jan 2009
TUNGSTEN TSV
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30um pitch (32 TSVs)
40um pitch (32 TSVs)
With TSV
Observed TSV capacitance behavior for the first time from measurement
2-bar W-TSV:
1.5 um wide6 um long10 um pad0.5 um thick oxide25 um tall5 um bar-to-bar separation30um/40um pitch (TSV-to-TSV)
Xerxes TV: A 300-mm wafer-level 3DI process using W-TSV and hybrid Cu/adhesive wafer bonding for BEOL; technology reported in IEDM, Dec, 2008 (Liu, F., et al.); TSV L/C/RF test sites measurement/characterization completed in Apr. 2009.
Without TSV
Independent measurements (YKT) confirm the silicon dielectric relaxation strong effectTUNGSTEN TSV
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A deeper study: Cu or W TSV?RDC(via diameter) of cylindrical Cu TSV (oxide th =0.5 um)
vs. tungsten TSV structures, for the same TSV length=70um
0.00
0.02
0.04
0.06
0.08
0.10
0.12
0.14
0.16
5 7.5 10 12.5 15 17.5 20
Cu via diameter, um
R, O
hm
cylindrical Cu, R(via diameter)
R(4 bar W)
maxR=2mV/200mA=10 mOhm
Cu TSV with diameter >12.5 um meets the max current requirements
CDC(via diameter) of annular copper TSV (oxide th =0.5 um) vs. tungsten TSV structures, for the same TSV length=70um
75
175
275
375
475
575
675
5 7.5 10 12.5 15 17.5 20
Cu via diameter, um
C, f
F
annular Cu, C(via diameter)
C(1 long bar W)
C(4 bar W)
Cu TSV with diameter <12.5 um, oxide liner th=0.5 um is better than both tungsten TSV structures
CDC(oxide thickness) of annular fat copper TSV (D=21 um) vs. tungsten TSV structures, for the same TSV length=70um
175
275
375
475
575
675
0.5 0.6 0.7 0.8 0.9 1oxide thickness, um
C, f
F
annular fat Cu, C(oxide thickness)
C(1 long bar W)
C(4 bar W)
Fat Cu TSV with oxide liner th>0.9 um is better than both W TSV structures
Electrical considerations: bottom line Currently suggested Cu TSV is better Thicker Cu TSV oxide liner is desirable Smaller Cu TSV diameter is desirable
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wq via - 1.0 um thick Cu
oa wiring level – 3.0 um thick Cu
tv stack
0.1 um nblock k=5.3
0.2 um nitride k=7.0
0.65 oxide um k=4.1
td - 1.2 um AL is wide enough (36 um) to shield the bump from upper layers
fv stack
0.45 um nitride k=7.0
0.45 nm oxide k=4.1
tm stack
0.1 um Ti/W
0.43 um Cu
1.0-2.0 um Ni ( 1.0 um likely )
0.05 um Au
uC4
10-15 um Pb free bump ( closer to 15 um likely) - 15 um in the model Contacts resistance = ?
wk metal stack
0.1 um Ti/W
0.5 um Cu
1.0-2.0 um Ni - 1.0 um in the model 0.05 um Au ( no Au if plating solder )
pbSn ( need Au for lead free )
3DI vertical interconnect based on Cu annular TSV:tech input and models scope
wi metal stack
0.1 um Ti/W
0.5 um Cu
wj opening
1.0 um nitride
oxide cap 1.0 um
uC4model domain
TSVmodel domain
To beextracted
underfill k=3.824
ESCHER
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Copper annular TSV model scope – side view
WI backside Cu endplate: 36x36um, th=0.5umDielectric over the silicon: k=4.1, th=1um
TSV part surrounded by silicon: Cu diameter = 21 umsilicon thickness = [30..70] um, thnom = 50umk =11.9, sigma = 0.135 Ohm*moxide liner th = [0.6..1.5] um, thnom = 0.5 um
TSV part surrounded by BEOL: BEOL thickness = 5.05 um BEOL effective keepout square 25.33x25.33umBEOL effective k = 4.1
UA frontside Cu endplate: 24.2x24.2um, thickness = 1.2 um UA keepout width = 25.8 um
TSVmodel domain
Note: Black – constant values Green – model parameters
ESCHER
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Copper annular TSV model Top view
TSV XY pitch = 46.4 um
46.4 um
Cu diameter = 21 um
Core diameter = 6 um
oxide coat th = [0.6..1.5] um, thnominal = 0.5 um
TSV corner parameter [-1 ..1] considers the 8 neighbor TSV’s impact Corner = -1: neighbors bear “hostile” signals Corner = 0: neighbors are ground/VDD Corner = 1: neighbors bear “friendly” signals
Modeled TSV
Note: Black – constant values Green – model parameters
ESCHER
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Copper Annular TSV Model vs. EM Solver
RLCG for TSV length=50 um, oxide thickness=0.6 um, Corner = 0
ESCHER
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wq via - 1.0 um thick Cu
oa wiring level – 3.0 um thick Cu
tv stack
0.1 um nblock k=5.3
0.2 um nitride k=7.0
0.65 oxide um k=4.1
td - 1.2 um AL is wide enough (36 um) to shield the bump from upper layers
fv stack
0.45 um nitride k=7.0
0.45 nm oxide k=4.1
tm stack
0.1 um Ti/W
0.43 um Cu
1.0-2.0 um Ni ( 1.0 um likely )
0.05 um Au
uC4
10-15 um Pb free bump ( closer to 15 um likely) - 15 um in the model Contacts resistance = ?
wk metal stack
0.1 um Ti/W
0.5 um Cu
1.0-2.0 um Ni - 1.0 um in the model 0.05 um Au ( no Au if plating solder )
pbSn ( need Au for lead free )
uC4 Model Scope: Side View
wi metal stack
0.1 um Ti/W
0.5 um Cu
wj opening
1.0 um nitride
oxide cap 1.0 um
uC4model domain
TSVmodel domain
To beextracted
underfill k=3.824
ESCHER
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uC4 model scope – Top View
uc4 XY pitch = 46.4 um
46.4 um
uC4 diameter = 24 um
uC4 corner parameter [-1 ..1] considers the 8 neighbor uC4’s impact Corner = -1: neighbors bear “hostile” signals Corner = 0: neighbors are ground/VDD Corner = 1: neighbors bear “friendly” signals
Modeled uC4
ESCHER
IBM Labs in Haifa
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Extraction scope - parameters
2.4
(OA width > 6 μm) min space ≥ 2.4
Neighbors: wide wires
0.8
UB connection: 1power wire removedNeighbors: w=2.4 um, s = 0.8 um nested
1.2
3.0
0.95
1.2
1.6
1.0
0.9
ub 24.2x2.4
14
uC4model domain
TSVmodel domain
To beextracted
ESCHER
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“Extracted” part: worst case close neighbors in OA and UB (min DRC away)
C = 54.2 fF
ESCHER
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“Extracted” part: best caseneighbors in OA and UB are far away
C=8.96 fF
ESCHER
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Sample Simulated Results5 Signal Lines: CPW vs. RC vs. EM Solver, 11000 mode, S-parameter format stack: 323102, signal in UB, crossing in UA, parallel in E1, w=s=2um, d=3um
1mm lines, simulation from 10[MHz] up to 50[GHz]
IBM Labs in Haifa
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Cu-TSV W-TSV
1 Gb/s 10 Gb/s
Cu-TSV W-TSV
TSV Haifa circuit level models enable high-speed I/O analysis for 3D electrical link !
driver
receiver
3 cascaded TSVs connected by uC4
pattern generator
I/O simulation using Escher TSV models for 3D design (YKT)
ESCHER
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Haifa broadband TSV test cage on Escher 3DI 45nm test site
ESCHER
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TSV capacitance measurements vs. modelResults at 1MHz
4:4C=932 fF
2:2C=497 fF
6:6C=1369 fF
OpenC=71.5 fF
Signal to grounded chuck capacitance measurements
Signal to chuck capacitance de-embeddingFor n=2, 4, 6: Cmeasured (n) = Copen + n*CTSV + (n-2)*Cconnector
For n=2: CTSV = 212.75 fFFor n=4, 6: CTSV = 211.75 fF,
Cconnector = 6.75 fF
(parallel plate estimation Cconnector ~ 7.2fF)
Measured Escher TSV capacitance at zero bias = 212 fFModeled low freq. capacitance (oxide liner th = 0.7um) = 227 fF
ESCHER
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Depletion-mode Capacitance Effect on TSV Performance (YKT)
Depletion effect improves TSV signal integrity (estimated ~17% reduction of TSV low freq C for Escher); Capacitance test sites added on EV0/Escher TV for measurement and characterization
Potential new applications: e.g., tune TSV capacitance to change signal timing
r0r1
r2Cu
Oxide liner
Depletion region
( Source: SRC Project IBM-Georgia Tech)
Coxide CdepletionDepletion effect reduces TSV low frequency capacitance
C_TSVC_oxide
Escher TSV diameter
The depletion effect is relatively smallTo estimate it, low frequency measurements are required
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TSV measurements vs. model preliminary results: 2:2 CG up to 50GHz
Even mode
S GG GGGG G G
ESCHER
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Architecture of TeraMos FPA for Passive Terahertz Imaging (0.6-1.5 THz)
pixels for 1.5THz: 200µm*200µm – higher resolution pixels for 0.6THz: 500µm*500µm – higher clothes penetration Adapting the required pixel dimensions by applying a novel
variable pixel concept based on readout circuitry
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We have conceived, designed and modeled a maximal flexibility Variable T-line device in IBM 32nm SOI technology.
Tuning resolution of 4 bit was found practical and sufficient. Optimized design yields high delay tuning range of ~20%. Works well within a dedicated matching network enabling
flexible design styles. Minimal area on silicon and minimal power consumption to
operate. Dedicated existing versions enable multiple background
impedances, fine length tuning resolution, and higher frequency bandwidth exact modeling.
Variable Delay T-lines SUMMARY
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TSV model results: RLCG up to 60GHz z360 (22nm)
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S-parameters for a simple microstrip structure with parameters: w=4.5um, h=10.45, t=4um, wg=33.4, tg=0.32, length of the microstrip is 150um
Aluminum signal layer (sigma =3.57e7 siemens/meter), Copper ground layer (sigma = 3.48e7 siemens/meter)silicon oxide dielectric (relative epsilon = 4.1)
w
signal
ground
h
t
wg
tg
w
signal
ground
h
t
wg
tg
T-line EM solver results up to 1THz
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June 1998 – Research starts at IBM Haifa Research Labs January 2000 – Start of joint work with IBM FAB (Burlington) Design
Automation Department January 2001 – Haifa T-line models inside IBM Design kit January 2002 – Haifa owns T-line model and design R&D for all IBM
leading edge chip technologies December 2002 – IBM Research Accomplishment Award Jan 2005 – T-line models upgraded to include crossing lines and full
closed environment consideration April 2005 – 60GHz on chip 4:1 transformer based on T-line theory August 2005 – T-lines used in a the big IBM Loki project (Xbox 360) Dec 2007 - IBM Outstanding Research Accomplishment Award 2008 – 3DI TSV / mC4 modeling startup 2009 – THz level T-line devices + THz imaging research (MEMS) startup Till 2011 – 18 patents, 22 publications
IBM On-Chip Interconnect Project History
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Standard CMOS upper metal layers (Al) provide masking for post-processing
(a) CMOS-SOI Wafer Fabrication in Standard FAB
(b) Back-Side DRIE Anisotropic Etching of SiliconBOX provides etch stop
(c) Front Side RIE Etching of ILD using CHF3flourine plasma does not etch Al Masks
(d) Front Side Metal Mask Wet Etching
The MEMS Post-Processing
Currently performed at the Technion
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TargetProvide means to design circuits including on-chip critical wiring enabling precise prediction of the expected circuit behavior
Required solution features Designer friendly
simple and very fast in operation does not require a deep electromagnetic understanding “protects the designer against himself” supports the given specific technology details (given metal stack,
dielectric structure etc.)
Should provide high broadband accuracy for both A&MS and digital design (at least from DC up to 3rd signal harmonic) in actual design environment (including crossing lines, silicon substrate etc.)
Fully integrated within common design flows (e.g., Cadence, CTE)
Supports all simulation kinds: transient, AC, S-Parameter, PSS
On-Chip Interconnect Design and Modeling Challenge