ltc2203/ltc2202 - 16-bit, 25msps/10msps adc...ltc2203/ltc2202 1 22032fd 16-bit, 25msps/10msps adcs...

LTC2203/LTC2202

122032fd

16-Bit, 25Msps/10Msps ADCs

The LTC®2203/LTC2202 are 25Msps/10Msps, sampling 16-bit A/D converters designed for digitizing high frequen-cy, wide dynamic range signals with input frequencies up to 380MHz. The input range of the ADC can be optimized with the PGA front end.

The LTC2203/LTC2202 are perfect for demanding app-lications, with AC performance that includes 81.6dB SNR and 100dB spurious free dynamic range (SFDR). Maximum DC specs include ±4LSB INL, ±1LSB DNL (no missing codes).

A separate output power supply allows the CMOS output swing to range from 0.5V to 3.6V.

A single-ended CLK input controls converter operation. An optional clock duty cycle stabilizer allows high performance at full speed with a wide range of clock duty cycles. L, LT, LTC, LTM, Linear Technology and the Linear logo are registered trademarks of Linear Technology Corporation. All other trademarks are the property of their respective owners. Protected by U.S. Patents including 4843302, 6949965B1.n Telecommunications

n Receiversn Cellular Base Stationsn Spectrum Analysisn Imaging Systemsn ATE

n Sample Rate: 25Msps/10Mspsn 81.6dB SNR and 100dB SFDR (2.5V Range)n SFDR 90dB at 70MHz (1.667VP-P Input Range)n PGA Front End (2.5VP-P or 1.667VP-P Input Range)n 380MHz Full Power Bandwidth S/Hn Optional Internal Dithern Optional Data Output Randomizern Single 3.3V Supplyn Power Dissipation: 220mW/140mWn Clock Duty Cycle Stabilizern Out-of-Range Indicatorn Pin Compatible Family 25Msps: LTC2203 (16-Bit)

10Msps: LTC2202 (16-Bit)n 48-Pin (7mm × 7mm) QFN Package

–

+S/HAMP

CORRECTIONLOGIC AND

SHIFT REGISTER

OUTPUTDRIVERS

16-BITPIPELINEDADC CORE

INTERNAL ADCREFERENCEGENERATOR

1.25VCOMMON MODEBIAS VOLTAGE

CLOCK/DUTYCYCLE

CONTROL

CLK PGA SHDN DITH MODE RAND

VCM

ANALOGINPUT

22032 TA01

D15•••

D0

CMOS

OUTPUTS

0.5V TO 3.6V

3.3V

3.3V

SENSE

OGND

OVDD

2.2μF 1μF

1μF 1μF 1μF

VDD

GND

ADC CONTROL INPUTS

AIN+

AIN–

OF

CLKOUT+

CLKOUT–

OE

FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 TA02

LTC2203: 128K Point FFT,fIN = 5.1MHz, –1dBFS, PGA = 0

FEATURES DESCRIPTION

APPLICATIONS

TYPICAL APPLICATION

LTC2203/LTC2202

222032fd

TOP VIEW

UK PACKAGE48-LEAD (7mm 7mm) PLASTIC QFN

SENSE 1

VCM 2

VDD 3

VDD 4

GND 5

AIN+ 6

AIN– 7

GND 8

GND 9

CLK 10

GND 11

VDD 12

36 OVDD

35 D11

34 D10

33 D9

32 D8

31 OGND

30 CLKOUT+

29 CLKOUT–

28 D7

27 D6

26 D5

25 OVDD

48 G

ND

47 P

GA

46 R

AN

D

45 M

OD

E

44OE

43 O

F

42 D

15

41 D

14

40 D

13

39 D

12

38 O

GN

D

37 O

VD

D

VD

D13

VD

D 1

4

GN

D 1

5

SH

DN

16

DIT

H17

D0 1

8

D1

19

D2

20

D3 2

1

D4 2

2

OG

ND

23

OV

DD

24

49

EXPOSED PAD IS GND (PIN 49)MUST BE SOLDERED TO PCB BOARD

TJMAX = 150°C, θJA = 29°C/W

Supply Voltage (VDD) .................................. –0.3V to 4VDigital Output Supply Voltage (OVDD) ......... –0.3V to 4VDigital Output Ground Voltage (OGND) ....... –0.3V to 1VAnalog Input Voltage (Note 3) .... –0.3V to (VDD + 0.3V) Digital Input Voltage ................... –0.3V to (VDD + 0.3V)Digital Output Voltage ............... –0.3V to (OVDD + 0.3V)Power Dissipation ............................................2000mWOperating Temperature Range LTC2203C/LTC2202C ............................. 0°C to 70°C LTC2203I/LTC2202I ............................ –40°C to 85°CStorage Temperature Range ................. –65°C to 150°C

OVDD = VDD (Notes 1 and 2)

ABSOLUTE MAXIMUM RATINGS PIN CONFIGURATION

ORDER INFORMATIONLEAD FREE FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE

LTC2203CUK#PBF LTC2203CUK#TRPBF LTC2203UK 48-Lead (7mm × 7mm) Plastic QFN 0°C to 70°C

LTC2202CUK#PBF LTC2202CUK#TRPBF LTC2202UK 48-Lead (7mm × 7mm) Plastic QFN 0°C to 70°C

LTC2203IUK#PBF LTC2203IUK#TRPBF LTC2203UK 48-Lead (7mm × 7mm) Plastic QFN –40°C to 85°C

LTC2202IUK#PBF LTC2202IUK#TRPBF LTC2202UK 48-Lead (7mm × 7mm) Plastic QFN –40°C to 85°C

LEAD BASED FINISH TAPE AND REEL PART MARKING* PACKAGE DESCRIPTION TEMPERATURE RANGE

LTC2203CUK LTC2203CUK#TR LTC2203UK 48-Lead (7mm × 7mm) Plastic QFN 0°C to 70°C

LTC2202CUK LTC2202CUK#TR LTC2202UK 48-Lead (7mm × 7mm) Plastic QFN 0°C to 70°C

LTC2203IUK LTC2203IUK#TR LTC2203UK 48-Lead (7mm × 7mm) Plastic QFN –40°C to 85°C

LTC2202IUK LTC2202IUK#TR LTC2202UK 48-Lead (7mm × 7mm) Plastic QFN –40°C to 85°C

Consult LTC Marketing for parts specifi ed with wider operating temperature ranges. *The temperature grade is identifi ed by a label on the shipping container.

For more information on lead free part marking, go to: http://www.linear.com/leadfree/ For more information on tape and reel specifi cations, go to: http://www.linear.com/tapeandreel/

LTC2203/LTC2202

322032fd

CONVERTER CHARACTERISTICS

PARAMETER CONDITIONS MIN TYP MAX UNITS

Resolution (No missing codes) 16

Integral Linearity Error Differential Analog Input (Note 5) TA = 25°C ±1.2 ±4.0 LSB

Integral Linearity Error Differential Analog Input (Note 5) l ±1.5 ±4.5 LSB

Differential Linearity Error Differential Analog Input l ±0.3 ±1 LSB

Offset Error (Note 6) l ±2 ±10 mV

Offset Drift ±10 μV/°C

Gain Error External Reference l ±0.2 ±1.5 %FS

Full-Scale Drift Internal ReferenceExternal Reference

±30±15

ppm/°Cppm/°C

Transition Noise External Reference (2.5V Range, PGA = 0) 1.92 LSBRMS

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

VIN Analog Input Range (AIN+ – AIN

–) 3.135V ≤ VDD ≤ 3.465V 1.667 or 2.5 VP-P

VIN, CM Analog Input Common Mode Differential Input (Note 7) l 1 1.25 1.5 V

IIN Analog Input Leakage Current 0V ≤ AIN+, AIN

– ≤ VDD (Note 9) l –1 1 μA

ISENSE SENSE Input Leakage Current 0V ≤ SENSE ≤ VDD (Note 10) l –3 3 μA

IMODE MODE Pin Pull-Down Current to GND 10 μA

IOE OE Pin Pull-Down Current to GND 10 μA

CIN Analog Input Capacitance Sample Mode CLK = 0Hold Mode CLK = 0

10.51.4

pFpF

tAP Sample-and-HoldAcquisition Delay Time

0.9 ns

tJITTER Sample-and-HoldAcquisition Delay Time Jitter

200 fSRMS

CMRR Analog InputCommon Mode Rejection Ratio

1V < (AIN+ = AIN

–) <1.5V 80 dB

BW-3dB Full Power Bandwidth Rs < 20Ω 380 MHz

SYMBOL PARAMETER CONDITIONS MINLTC2203

TYP MAX MINLTC2202

TYP MAX UNITS

SNR Signal-to-Noise Ratio 1MHz Input (2.25V Range, PGA = 0)1MHz Input (1.667V Range, PGA = 1)

81.679.4

81.679.4

dBFSdBFS

5MHz Input (2.5V Range, PGA = 0)5MHz Input (1.667V Range, PGA = 1)

l 80 81.679.4

80 81.679.4

dBFSdBFS

12.5MHz Input (2.5V Range, PGA = 0)12.5MHz Input (1.667V Range, PGA = 1)

81.479.3

81.479.3

dBFSdBFS

30MHz Input (2.5V Range, PGA = 0)30MHz Input (1.667V Range, PGA = 1) l 77.5

80.878.9 77.5

80.878.9

dBFSdBFS

70MHz Input (2.5V Range, PGA = 0)70MHz Input (1.667V Range, PGA =1 )

78.377.2

78.377.2

dBFSdBFS

ANALOG INPUT

DYNAMIC ACCURACY The l denotes the specifi cations which apply over the full operating temperature range, otherwise specifi cations are at TA = 25°C. AIN = –1dBFS. (Note 4)

The l denotes the specifi cations which apply over the full operating temperature range, otherwise specifi cations are at TA = 25°C. (Note 4)


LTC2203/LTC2202

422032fd

The l denotes the specifi cations which apply over the full operating temperature range, otherwise specifi cations are at TA = 25°C. AIN = –1dBFS. (Note 4)DYNAMIC ACCURACY


TYP MAX MINLTC2202

TYP MAX UNITS

SFDR Spurious Free Dynamic Range 2nd or 3rd Harmonic


100100

100100

dBcdBc

5MHz Input (2.5V Range, PGA = 0) 5MHz Input (2.5V Range, PGA = 0)5MHz Input (1.667V Range, PGA = 1)

l 8587

100100100

8587

100100100

dBcdBcdBc


95100

95100

dBcdBc

30MHz Input (2.5V Range, PGA = 0)30MHz Input (1.667V Range, PGA = 1) l 85

9095 85

9095

dBcdBc


8590

8590

dBcdBc

SFDR Spurious Free Dynamic Range 4th Harmonic or Higher


100100

100100

dBcdBc


l 90 100100

90 100100

dBcdBc


100100

100100

dBcdBc

30MHz Input (2.5V Range, PGA = 0)30MHz Input (1.667V Range, PGA = 1) l 90

100100 90

100100

dBcdBc


9090

9090

dBcdBc

S/(N+D) Signal-to-NoisePlus Distortion Ratio


81.579.3

81.579.3

dBFSdBFS


l 79.7 81.579.3

79.7 81.579.3

dBFSdBFS


81.379.2

81.379.2

dBFSdBFS

30MHz Input (2.5V Range, PGA = 0)30MHz Input (1.667V Range, PGA = 1) l 77.2

80.678.6 77.2

80.678.6

dBFSdBFS


78.177

78.177

dBFSdBFS

SFDR Spurious Free

Dynamic Range

at –25dBFS

Dither “OFF”


105105

105105

dBFSdBFS


105105

105105

dBFSdBFS


105105

105105

dBFSdBFS


105105

105105

dBFSdBFS


100100

100100

dBFSdBFS

LTC2203/LTC2202

522032fd

PARAMETER CONDITIONS MIN TYP MAX UNITS

VCM Output Voltage IOUT = 0 1.15 1.25 1.35 V

VCM Output Tempco IOUT = 0 ±40 ppm/°C

VCM Line Regulation 3.135V ≤ VDD ≤ 3.465V 1 mV/ V

VCM Output Resistance 1mA ≤ | IOUT | ≤ 1mA 2 Ω

COMMON MODE BIAS CHARACTERISTICS

SYMBOL PARAMETER CONDITIONS MIN TYP MAX UNITS

LOGIC INPUTS (CLK, OE, DITH, PGA, SHDN, RAND)

VIH High Level Input Voltage VDD = 3.3V l 2 V

VIL Low Level Input Voltage VDD = 3.3V l 0.8 V

IIN Digital Input Current VIN = 0V to VDD l ±10 μA

CIN Digital Input Capacitance (Note 7) 1.5 pF

LOGIC OUTPUTS

OVDD = 3.3V

VOH High Level Output Voltage VDD = 3.3V IO = –10μA IO = –200μA l 3.1

3.2993.29

VV

VOL Low Level Output Voltage VDD = 3.3V IO = 160μA IO = 1.6mA l

0.010.10 0.4

VV

ISOURCE Output Source Current VOUT = 0V –50 mA

ISINK Output Sink Current VOUT = 3.3V 50 mA

OVDD = 2.5V

VOH High Level Output Voltage VDD = 3.3V IO = –200μA 2.49 V

VOL Low Level Output Voltage VDD = 3.3V IO = 1.60mA 0.1 V

OVDD = 1.8V

VOH High Level Output Voltage VDD = 3.3V IO = –200μA 1.79 V

VOL Low Level Output Voltage VDD = 3.3V IO = 1.60mA 0.1 V

DIGITAL INPUTS AND DIGITAL OUTPUTS


TYP MAX MINLTC2202

TYP MAX UNITS

SFDR Spurious Free

Dynamic Range

at –25dBFS

Dither “ON”


115115

115115

dBFSdBFS


l 100 115115

100 115115

dBFSdBFS


115115

115115

dBFSdBFS


115115

115115

dBFSdBFS


110110

110110

dBFSdBFS

DYNAMIC ACCURACY The l denotes the specifi cations which apply over the full operating temperature range, otherwise specifi cations are at TA = 25°C. AIN = –1dBFS. (Note 4)



LTC2203/LTC2202

622032fd

TIMING CHARACTERISTICS

Note 1: Stresses beyond those listed under Absolute Maximum Ratings

may cause permanent damage to the device. Exposure to any Absolute

Maximum Rating condition for extended periods may affect device

reliability and lifetime.

Note 2: All voltage values are with respect to GND, with GND and OGND

shorted (unless otherwise noted).

Note 3: When these pin voltages are taken below GND or above VDD, they

will be clamped by internal diodes. This product can handle input currents

of greater than 100mA below GND or above VDD without latchup.

Note 4: VDD = 3.3V, fSAMPLE = 25MHz (LTC2203), 10MHz (LTC2202),

input range = 2.5VP-P with differential drive (PGA = 0), unless otherwise

specifi ed.

Note 5: Integral nonlinearity is defi ned as the deviation of a code from a

“best fi t straight line” to the transfer curve. The deviation is measured from

the center of the quantization band.

Note 6: Offset error is the offset voltage measured from –1/2LSB when the

output code fl ickers between 0000 0000 0000 0000 and 1111 1111 1111

1111 in 2’s complement output mode.

Note 7: Guaranteed by design, not subject to test.

Note 8: Recommended operating conditions.

Note 9: Dynamic current from switched capacitor inputs is large compared

to DC leakage current, and will vary with sample rate.

Note 10: Leakage current will experience transient at power up. Keep

resistance < 1K Ω.


The l denotes the specifi cations which apply over the full operating temperature range, otherwise specifi cations are at TA = 25°C. AIN = –1dBFS. (Note 4)


TYP MAX MINLTC2202

TYP MAX UNITS

VDD Analog Supply Voltage l 3.135 3.3 3.465 3.135 3.3 3.465 V

PSHDN Shutdown Power SHDN = VDD, CLK = VDD 2 2 mW

OVDD Output Supply Voltage l 0.5 3.6 0.5 3.6 V

IVDD Analog Supply Current l 66 80 42 50 mA

PDIS Power Dissipation l 220 264 140 165 mW

POWER REQUIREMENTS


TYP MAX MINLTC2202

TYP MAX UNITS

fS Sampling Frequency l 1 25 1 10 MHz

tL CLK Low Time Duty Cycle Stabilizer OffDuty Cycle Stabilizer On

l

l

18.95

2020

500500

405

5050

500500

nsns

tH CLK High Time Duty Cycle Stabilizer OffDuty Cycle Stabilizer On

l

l

18.95

2020

500500

405

5050

500500

nsns

tAP Sample-and-HoldAperture Delay

0.9 0.9 ns

tD CLK to DATA Delay CL = 5pF (Note 7) l 1.3 3.1 4.9 1.3 3.1 4.9 ns

tC CLK to CLKOUT Delay CL = 5pF (Note 7) l 1.3 3.1 4.9 1.3 3.1 4.9 ns

tSKEW DATA to CLKOUT Skew CL = 5pF (Note 7) l –0.6 0 0.6 –0.6 0 0.6 ns

DATA Access TimeBus Relinquish Time

CL = 5pF (Note 7)(Note 7)

l

l

55

1515

55

1515

nsns

PipelineLatency

7 7 Cycles

LTC2203/LTC2202

722032fd

LTC2203: Integral Nonlinearity (INL) vs Output Code

LTC2203: Differential Nonlinearity (DNL) vs Output Code

LTC2203: AC Grounded Input Histogram (256k Samples)

LTC2203: 128K Point FFT, fIN = 1MHz, –1dBFS, PGA = 0



CODE

0

INL E

RR

OR

(LS

B)

0.0

0.5

1.0

65536

22032 G01

–0.5

–1.0

–2.016384 32768 49152

–1.5

2.0

1.5

CODE

0–1.0

DN

L E

RR

OR

(LS

B)

–0.8

–0.4

–0.2

0.0

1.0

0.4

16384 32768

22032 G02

–0.6

0.6

0.8

0.2

49152 65536

OUTPUT CODE

328120

CO

UN

T

10000

20000

30000

40000

50000

60000

32816 32820 32824 32828

22032 G03

32832

FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 GO4FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 GO6

tAP

ANALOGINPUT

tH

tD

tC

tL

N – 7 N – 6 N – 5 N – 4 N – 3

CLK

CLKOUT+

CLKOUT–

D0-D15, OF

22032 TD01

N + 1

N + 2

N + 4

N + 3N

TIMING DIAGRAM

TYPICAL PERFORMANCE CHARACTERISTICS

LTC2203/LTC2202

822032fd

LTC2203: 128K Point FFT, fIN = 5.1MHz, –20dBFS, PGA = 0,Internal Dither “On”

LTC2203: 32K Point 2-Tone FFT, fIN = 4.9MHz and 30.1MHz, –7dBFS, PGA = 0


LTC2203: SFDR vs Input Level,fIN = 5MHz, PGA = 0, Dither “Off”

LTC2203: SFDR vs Input Level,fIN = 5MHz, PGA = 0, Dither “On”

LTC2203: 32K Point FFT, fIN = 12.4MHz, –1dBFS, PGA = 0

FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 G10FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 G12

INPUT LEVEL (dBFS)

–70

SFD

R (

dB

c A

ND

dB

FS)

80

100

120

22032 G13

60

40

–60 –50 –40 –30 –20 –10 0

20

0

140

INPUT LEVEL (dBFS)

–70

SFD

R (

dB

c A

ND

dB

FS)

80

100

120

22032 G14

60

40

–60 –50 –40 –30 –20 –10 0

20

0

140

FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 G15


FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 GO7


LTC2203: 128K Point FFT, fIN = 5.1MHz, –20dBFS, PGA = 0,Internal Dither “Off”

FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 GO9


LTC2203/LTC2202

922032fd



LTC2203: SFDR vs Input Level, fIN = 12.7MHz, PGA = 0, Dither “Off”

FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 G17 INPUT LEVEL (dBFS)

–70

SFD

R (

dB

c A

ND

dB

FS)

80

100

120

22032 G18

60

40

–60 –50 –40 –30 –20 –10 0

20

0

140

LTC2203: SFDR vs Input Level, fIN = 12.7MHz, PGA = 0, Dither “On”






INPUT LEVEL (dBFS)

–70

SFD

R (

dB

c A

ND

dB

FS)

80

100

120

22032 G19

60

40

–60 –50 –40 –30 –20 –10 0

20

0

140

FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 G21

FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 G22INPUT LEVEL (dBFS)

–80

SFD

R (

dB

c A

ND

dB

FS)

80

100

120

22032 G23

60

40

–70 –60 –50 –40 –30 –20 –10 0

20

0

140

INPUT LEVEL (dBFS)

–70

SFD

R (

dB

c A

ND

dB

FS)

80

100

120

22032 G24

60

40

–60 –50 –40 –30 –20 –10 0

20

0

140


LTC2203/LTC2202

1022032fd



LTC2203: SFDR vs Input Level,fIN = 70.1MHz, PGA = 0,Dither “Off”

LTC2203: SFDR vs Input Level,fIN = 70.1MHz, PGA = 0,Dither “On”

LTC2203: SFDR (HD2 or HD3) vs Input Frequency LTC2203: SNR vs Input Frequency

FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 G29 INPUT LEVEL (dBFS)–70 –60 –50 –40 –30 –20 –10 0

SFDR

(dbc

AND

dBF

S)80

100

120

22032 G30

60

40

20

0

140

INPUT LEVEL (dBFS)

–70

SFD

R (

dB

c A

ND

dB

FS)

80

100

120

22032 G31

60

40

–60 –50 –40 –30 –20 –10 0

20

0

140

INPUT FREQUENCY (MHz)

0

SFD

R (

dB

c)

85

90

95

60 100

22032 G32

80

75

7020 40 80

100

105

110

PGA = 1

PGA = 0


073

SN

R (

dB

FS)

74

76

77

78

80

82

22032 G33

75

4020 100 12060 140

79

80

81PGA = 0

PGA = 1




FREQUENCY(MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–10

–30

–50

–70

–90

–110

–130

–40

2 6

–20

–60

4 8 10 12

22032 G27


LTC2203/LTC2202

1122032fd

LTC2203: SNR and SFDR vs Sample Rate

LTC2203: SNR and SFDR vs Supply Voltage (VDD), fIN = 5MHz

LTC2203: IVDD vs Sample Rate, 5MHz Sine Wave, –1dBFS

SAMPLE RATE (Msps)0

75

SNR

AND

SFDR

(dBF

S)

80

90

95

100

110

5 25 35

22032 G34

85

105

20 45 5010 15 30 40

SFDRRATED MAX

SNR

SUPPLY VOLTAGE (V)

2.8

SN

R S

FDR

(dB

FS)

95

100

105

3.4 3.5

22032 G35

90

85

2.9 3.0 3.1 3.2 3.3 3.6

80

75

110

SFDR

LOWER LIMIT UPPER LIMIT

SNR

SAMPLE RATE (Msps)

0

I VD

D (

mA

) 65

70

75

20

22032 G36

60

55

505 10 15 25

LTC2203: Normalized Full Scale vs Temperature, Internal Reference, 5 Units

LTC2203: Offset Voltage vs Temperature, 5 Units

LTC2203: SFDR vs Input Common Mode Voltage, fIN = 5MHz, –1dBFS, PGA = 0

LTC2202: Integral Nonlinearity (INL) vs Output Code

LTC2202: Differential Nonlinearity (DNL) vs Output Code

LTC2202: AC Grounded Input Histogram (256K Samples)

TEMPERATURE (°C)

–400.99

NO

RM

ALIZ

ED

FU

LL S

CA

LE

0.995

1

1.005

1.01

–20 0 20 40

22032 G37

60 80

TEMPERATURE (˚C)

–40

OFF

SET V

OLT

AG

E (

mV

)

2

4

6

20 60

22032 G38

0

–2

–20 0 40 80

–4

–6

INPUT COMMON MODE VOLTAGE (V)

0.560

SFD

R (

dB

c)

70

80

90

0.75 1 1.25 1.50

22032 G39

1.75

100

110

65

75

85

95

105

2

CODE

0

INL E

RR

OR

(LS

B)

0

0.5

1.0

65536

22032 G40

–0.5

–1.0

–2.016384 32768 49152

–1.5

2.0

1.5

CODE

01.0

DN

L E

RR

OR

(LS

B)

0.8

0.4

0.2

0

1.0

0.4

16384 32768

22032 G41

0.6

0.6

0.8

0.2

49152 65536

OUTPUT CODE

32793

CO

UN

T

40000

35000

30000

25000

15000

5000

45000

50000

32797

22032 G42

20000

10000

032801 32805 32809


LTC2203/LTC2202

1222032fd

LTC2203: 128K Point FFT, fIN = 5.1MHz, –20dBFS, PGA = 0,Internal Dither “On”



LTC2202: SFDR vs Input Level, fIN = 5MHz, PGA = 0, Dither “Off”

LTC2202: SFDR vs Input Level, fIN = 5MHz, PGA = 0, Dither “On”


FREQUENCY (MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5

22032 G46FREQUENCY (MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5

22032 G48

INPUT LEVEL (dBFS)

–700

SFD

R (

dB

c A

ND

dB

FS)

20

40

60

80

–60 –40 –20 0

22032 G49

100

120

–50 –30 –10

INPUT LEVEL (dBFS)

–700

SFD

R (

dB

c A

ND

dB

FS)

40

20

60

80

100

–60 –40 –20 0

22032 G50

120

140

–50 –30 –10

FREQUENCY (MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5

22032 G51



LTC2202: 128K Point FFT, fIN = 5.1MHz, –20dBFS, PGA = 0,Internal Dither “Off”

FREQUENCY (MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5

22032 G45


LTC2203/LTC2202

1322032fd



LTC2202: SFDR vs Input Level, fIN = 12.4MHz, PGA = 0, Dither “Off

FREQUENCY (MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5

22032 G53INPUT LEVEL (dBFS)

–700

SFD

R (

dB

c A

ND

dB

FS)

20

40

60

80

–60 –40 –20 0

22032 G54

100

120

–50 –30 –10







FREQUENCY (MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5

22032 G57

INPUT LEVEL (dBFS)

–700

SFD

R (

dB

c A

ND

dB

FS)

40

20

60

80

100

–60 –40 –20 0

22032 G58

120

140

–50 –30 –10

INPUT LEVEL (dBFS)

–700

SFD

R (

dB

c A

ND

dB

FS)

40

20

60

80

100

–60 –40 –20 0

22032 G59

120

140

–50 –30 –10

FREQUENCY (MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5

22032 G60


LTC2203/LTC2202

1422032fd




LTC2202: SFDR (HD2 or HD3) vs Input Frequency LTC2202: SNR vs Input Frequency

FREQUENCY (MHz)

–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

–20

–60

–130

–110

–90

–10

–50

–30

–70

22032 G64

0 2 4

INPUT LEVEL (dBFS)

–800

SFD

R (

dB

c A

ND

dB

FS)

40

20

60

80

100

–60 –40 –20 0

22032 G65

120

140

–70 –50 –30 –10

INPUT LEVEL (dBFS)

–800

SFD

R (

dB

c A

ND

dB

FS)

40

20

60

80

100

–60 –40 –20 0

22032 G66

120

140

–70 –50 –30 –10


0

SFD

R(d

Bc)

85

90

95

60 100

22032 G67

80

75

7020 40 80

100

105

110

PGA = 0

PGA = 1


073

SN

R (

dB

FS)

74

76

77

78

80

82

22032 G68

75

4020 100 12060 140

79

80

81

PGA = 0

PGA = 1


FREQUENCY (MHz)

–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

–20

–60

–130

–110

–90

–10

–50

–30

–70

22032 G63

0 2 4



FREQUENCY (MHz)

0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5


0–140

AM

PLIT

UD

E (

dB

FS)

–120

–100

–80

0

–40

1 3 4

–20

–60

–130

–110

–90

–10

–50

–30

–70

2 5

22032 G62


LTC2203/LTC2202

1522032fd

LTC2202: SNR and SFDR vs Sample Rate

LTC2202: SNR and SFDR vs Supply Voltage (VDD), fIN = 5MHz

LTC2202: IVDD vs Sample Rate, 5MHz Sine Wave, –1dBFS

LTC2202: Normalized Full Scale vs Temperature, Internal Reference, 5 Units

SAMPLE RATE (Msps)

0

100

105

110

16

22032 G69

95

90

4 8 12 20

85

80

75

SN

R A

ND

SFD

R (

dB

FS)

SFDR

RATED MAX

SNR

SUPPLY VOLTAGE (V)

2.8 2.9 3.0 3.1 3.2 3.3 3.4 3.5 3.6

SN

R S

FDR

(dB

FS)

95

100

105

22032 G70

90

85

80

75

110

SFDR

LOWER LIMIT UPPER LIMIT

SNR

SAMPLE RATE (Msps)

0

I VD

D (

mA

) 46

48

50

8

22032 G71

44

42

45

47

49

43

41

402 4 6 10

TEMPERATURE (°C)

–400.99

NO

RM

ALIZ

ED

FU

LL S

CA

LE

0.995

1

1.005

1.01

–20 0 20 40

22032 G72

60 80

TEMPERATURE (˚C)

–40

OFF

SET V

OLTA

GE (

mV

)

2

4

6

20 60

22032 G73

0

–2

–20 0 40 80

–4

–6

INPUT COMMON MODE VOLTAGE (V)

0.560

SFD

R (

dB

c)

70

80

90

0.75 1 1.25 1.50

22032 G74

1.75

100

110

65

75

85

95

105

2

LTC2202: Offset Voltage vs Temperature, 5 Units

LTC2202: SFDR vs Input Common Mode Voltage, fIN = 5MHz, –1dBFS, PGA = 0


TIME AFTER WAKE-UP OR CLOCK START (μs)

0

FULL-S

CA

LE E

RR

OR

(%

)

0.2

0.6

1.0

400

22032 G75

–0.2

–0.6

0

0.4

0.8

–0.4

–0.8

–1.010050 200150 300 350 450250 500

TIME FROM WAKE-UP OR CLOCK START (μs)

0

FULL-S

CA

LE E

RR

OR

(%

)

1

3

5

800

22032 G76

–1

–3

0

2

4

–2

–4

–5200100 400300 600 700 900500 1000

Mid-Scale Settling After WakeUp from Shutdown or Starting Encode Clock

Full-Scale Settling After WakeUp from Shutdown or Starting Encode Clock

LTC2203/LTC2202

1622032fd

SENSE (Pin 1): Reference Mode Select and External Refer-ence Input. Tie SENSE to VDD with 1k Ω or less to select the internal 2.5V bandgap reference. An external reference of 2.5V or 1.25V may be used; both reference values will set a full scale ADC range of 2.5V (PGA = 0).

VCM (Pin 2): 1.25V Output. Optimum voltage for input com-mon mode. Must be bypassed to ground with a minimum of 2.2μF. Ceramic chip capacitors are recommended.

VDD (Pins 3, 4, 12, 13, 14): 3.3V Analog Supply Pin. Bypass to GND with 0.1μF ceramic chip capacitors.

GND (Pins 5, 8, 9, 11, 15, 48, 49): ADC Power Ground.

AIN+ (Pin 6): Positive Differential Analog Input.

AIN– (Pin 7): Negative Differential Analog Input.

CLK (Pin 10): Clock Input. The hold phase of the sample-and-hold circuit begins on the falling edge. The output data may be latched on the rising edge of CLK.

SHDN (Pin 16): Power Shutdown Pin. SHDN = low results in normal operation. SHDN = high results in powered down analog circuitry and the digital outputs are placed in a high impedance state.

DITH (Pin 17): Internal Dither Enable Pin. DITH = low disables internal dither. DITH = high enables internal dither. Refer to Internal Dither section of this data sheet for details on dither operation.

D0-D15 (Pins 18-22, 26-28, 32-35 and 39-42): Digital Outputs. D15 is the MSB.

OGND (Pins 23, 31 and 38): Output Driver Ground.

OVDD (Pins 24, 25, 36, 37): Positive Supply for the Output Drivers. Bypass to ground with 0.1μF capacitor.

CLKOUT– (Pin 29): Data Valid Output. CLKOUT– will toggle at the sample rate. Latch the data on the falling edge of CLKOUT–.

CLKOUT+ (Pin 30): Inverted Data Valid Output. CLKOUT+ will toggle at the sample rate. Latch the data on the rising edge of CLKOUT+.

OF (Pin 43): Over/Under Flow Digital Output. OF is high when an over or under fl ow has occurred.

OE (Pin 44): Output Enable Pin. Low enables the digital output drivers. High puts digital outputs in Hi-Z state.

MODE (Pin 45): Output Format and Clock Duty Cycle Stabilizer Selection Pin. Connecting MODE to 0V selects offset binary output format and disables the clock duty cycle stabilizer. Connecting MODE to 1/3VDD selects offset binary output format and enables the clock duty cycle sta-bilizer. Connecting MODE to 2/3VDD selects 2’s complement output format and enables the clock duty cycle stabilizer. Connecting MODE to VDD selects 2’s complement output format and disables the clock duty cycle stabilizer.

RAND (Pin 46): Digital Output Randomization Selection Pin. RAND low results in normal operation. RAND high selects D1-D15 to be EXCLUSIVE-ORed with D0 (the LSB). The output can be decoded by again applying an XOR operation between the LSB and all other bits. The mode of operation reduces the effects of digital output interference.

PGA (Pin 47): Programmable Gain Amplifi er Control Pin. Low selects a front-end gain of 1, input range of 2.5VP-P. High selects a front-end gain of 1.5, input range of 1.667VP-P.

GND (Exposed Pad, Pin 49): ADC Power Ground. The ex-posed pad on the bottom of the package must be soldered to ground.

PIN FUNCTIONS

LTC2203/LTC2202

1722032fd

Figure 1. Functional Block Diagram

ADC CLOCKS

LOW JITTERCLOCKDRIVER

DITHERSIGNAL

GENERATOR

FIRST PIPELINEDADC STAGE

FIFTH PIPELINEDADC STAGE

FOURTH PIPELINEDADC STAGE

SECOND PIPELINEDADC STAGE

CLK

CORRECTION LOGICAND

SHIFT REGISTER

DITHM0DE

OGND

CLKOUT+

CLKOUT–

OF

D15

D14

OVDD

D1D0

22032 F01

INPUTS/H

AIN–

AIN+

THIRD PIPELINEDADC STAGE

OUTPUTDRIVERS

CONTROLLOGIC

PGA RANDSHDN

•••

VDD

GND

PGA

SENSE

VCMBUFFER

ADCREFERENCE

VOLTAGEREFERENCE

RANGESELECT

OE

BLOCK DIAGRAM

LTC2203/LTC2202

1822032fd

DYNAMIC PERFORMANCE

Signal-to-Noise Plus Distortion Ratio

The signal-to-noise plus distortion ratio [S/(N+D)] is the ratio between the RMS amplitude of the fundamental input frequency and the RMS amplitude of all other frequency components at the ADC output. The output is band lim-ited to frequencies above DC to below half the sampling frequency.

Signal-to-Noise Ratio

The signal-to-noise (SNR) is the ratio between the RMS amplitude of the fundamental input frequency and the RMS amplitude of all other frequency components, except the fi rst fi ve harmonics.

Total Harmonic Distortion

Total harmonic distortion is the ratio of the RMS sum of all harmonics of the input signal to the fundamental itself. The out-of-band harmonics alias into the frequency band between DC and half the sampling frequency. THD is expressed as:

THD = –20Log(√(V22 + V3

2 + V42 + ... VN

2)/V1)where V1 is the RMS amplitude of the fundamental fre-quency and V2 through VN are the amplitudes of the second through nth harmonics.

Intermodulation Distortion

If the ADC input signal consists of more than one spectral component, the ADC transfer function nonlinearity can produce intermodulation distortion (IMD) in addition to THD. IMD is the change in one sinusoidal input caused by the presence of another sinusoidal input at a different frequency.

If two pure sine waves of frequencies fa and fb are ap-plied to the ADC input, nonlinearities in the ADC transfer function can create distortion products at the sum and difference frequencies of mfa ± nfb, where m and n = 0, 1, 2, 3, etc. For example, the 3rd order IMD terms include (2fa + fb), (fa + 2fb), (2fa - fb) and (fa - 2fb). The 3rd order IMD is defi ned as the ratio of the RMS value of either input tone to the RMS value of the largest 3rd order IMD product.

Spurious Free Dynamic Range (SFDR)

The ratio of the RMS input signal amplitude to the RMS value of the peak spurious spectral component expressed in dBc. SFDR may also be calculated relative to full scale and expressed in dBFS.

Full Power Bandwidth

The Full Power bandwidth is that input frequency at which the amplitude of the reconstructed fundamental is reduced by 3dB for a full scale input signal.

Aperture Delay Time

The time from when CLK reaches 0.45 of VDD to the instant that the input signal is held by the sample-and-hold circuit.

Aperture Delay Jitter

The variation in the aperture delay time from conversion to conversion. This random variation will result in noise when sampling an AC input. The signal to noise ratio due to the jitter alone will be:

SNRJITTER = –20log (2π • fIN • tJITTER)

APPLICATIONS INFORMATION

LTC2203/LTC2202

1922032fd

CONVERTER OPERATION

The LTC2203/LTC2202 are CMOS pipelined multistep con-verters with a front-end PGA. As shown in Figure 1, the converter has fi ve pipelined ADC stages; a sampled analog input will result in a digitized value seven cycles later (see the Timing Diagram section). The analog input is differential for improved common mode noise immunity and to maximize the input range. Additionally, the differential input drive will reduce even order harmonics of the sample-and-hold circuit.

Each pipelined stage shown in Figure 1 contains an ADC, a reconstruction DAC and an interstage amplifi er. In operation, the ADC quantizes the input to the stage and the quantized value is subtracted from the input by the DAC to produce a residue. The residue is amplifi ed and output by the residue amplifi er. Successive stages oper-ate out of phase so that when odd stages are outputting their residue, the even stages are acquiring that residue and vice versa.

The phase of operation is determined by the state of the CLK input pin.

When CLK is high, the analog input is sampled differen-tially directly onto the input sample-and-hold capacitors, inside the “input S/H” shown in the block diagram. At the instant that CLK transitions from high to low, the volt-age on the sample capacitors is held. While CLK is low, the held input voltage is buffered by the S/H amplifi er which drives the fi rst pipelined ADC stage. The fi rst stage acquires the output of the S/H amplifi er during the low phase of CLK. When CLK goes back high, the fi rst stage produces its residue which is acquired by the second stage. At the same time, the input S/H goes back to acquiring the analog input. When CLK goes low, the second stage produces its residue which is acquired by the third stage. An identical process is repeated for the third and fourth stages, resulting in a fourth stage residue that is sent to the fi fth stage for fi nal evaluation.

Each ADC stage following the fi rst has additional range to accommodate fl ash and amplifi er offset errors. Results from all of the ADC stages are digitally delayed such that the results can be properly combined in the correction logic before being sent to the output buffer.

SAMPLE/HOLD OPERATION AND INPUT DRIVE

Sample/Hold Operation

Figure 2 shows an equivalent circuit for the LTC2203/LTC2202 CMOS differential sample and hold. The differ-ential analog inputs are sampled directly onto sampling capacitors (CSAMPLE) through NMOS transitors. The capacitors shown attached to each input (CPARASITIC) are the summation of all other capacitance associated with each input.

During the sample phase when CLK is high, the NMOS transistors connect the analog inputs to the sampling capacitors and they charge to, and track the differential input voltage. When CLK transitions from high to low, the sampled input voltage is held on the sampling capacitors. During the hold phase when CLK is high, the sampling capacitors are disconnected from the input and the held voltage is passed to the ADC core for processing. As CLK transitions from low to high, the inputs are reconnected to the sampling capacitors to acquire a new sample. Since the sampling capacitors still hold the previous sample, a charging glitch proportional to the change in voltage between samples will be seen at this time at the input of the converter. If the change between the last sample and

Figure 2. Equivalent Input Circuit

LTC2203/LTC2202

CLK

22032 F02

VDD

VDD

RPARASITIC3Ω

RPARASITIC3Ω

AIN+

AIN–

CPARASITIC1.4pF

CPARASITIC1.4pF

CSAMPLE9.1pF

CSAMPLE9.1pF

RON20Ω

RON20Ω


LTC2203/LTC2202

2022032fd

the new sample is small, the charging glitch seen at the input will be small. If the input change is large, such as the change seen with input frequencies near Nyquist, then a larger charging glitch will be seen.

Common Mode Bias

The ADC sample-and-hold circuit requires differential drive to achieve specifi ed performance. Each input may swing ±0.625V for the 2.5V range (PGA = 0) or ±0.417V for the 1.667V range (PGA = 1), around a common mode voltage of 1.25V. The VCM output pin (Pin 3) is designed to provide the common mode bias level. VCM can be tied directly to the center tap of a transformer to set the DC input level or as a reference level to an op amp differential driver circuit. The VCM pin must be bypassed to ground close to the ADC with 2.2μF or greater.

Input Drive Impedence

As with all high performance, high speed ADCs the dynamic performance of the LTC2203/LTC2202 can be infl uenced by the input drive circuitry, particularly the second and third harmonics. Source impedance and input reactance can infl uence SFDR. At the rising edge of CLK the sample and hold circuit will connect the 9.1pF sampling capacitor to the input pin and start the sampling period. The sampling period ends when CLK falls, hold-ing the sampled input on the sampling capacitor. Ideally, the input circuitry should be fast enough to fully charge the sampling capacitor during the sampling period 1/(2FCLK); however, this is not always possible and the incomplete settling may degrade the SFDR. The sampling glitch has been designed to be as linear as possible to minimize the effects of incomplete settling.

For the best performance it is recomended to have a source impedence of 100Ω or less for each input. The source impedence should be matched for the differential inputs. Poor matching will result in higher even order harmonics, especially the second.

INPUT DRIVE CIRCUITS

Figure 3 shows the LTC2203/LTC2202 being driven by an RF transformer with a center-tapped secondary. The secondary center tap is DC biased with VCM, setting the ADC input signal at its optimum DC level. Figure 3 shows a 1:1 turns

ratio transformer. Other turns ratios can be used; however, as the turns ratio increases so does the impedance seen by the ADC. Source impedance greater than 50Ω can reduce the input bandwidth and increase high frequency distor-tion. A disadvantage of using a transformer is the loss of low frequency response. Most small RF transformers have poor performance at frequencies below 1MHz.

Figure 3. Single-Ended to Differential Conversion Using a Transformer. Recommended for Input Frequencies from 1MHz to 100MHz

LTC2203/LTC2202

ANALOGINPUT

T1 = COILCRAFT WBCI-IT OR

MA/COM ETC1-1T.

RESISTORS, CAPACITORS ARE

0402 PACKAGE SIZE, EXCEPT 2.2μF.

22032 F03

0.1μF

2.2μF

12pF

12pF

12pF

0.1μF

T1

1:1

25Ω

25Ω

25Ω25Ω

VCM

AIN+

AIN–

Figure 4. Using a Transmission Line Balun Transformer. Recommended for Input Frequencies from 50MHz to 250MHz

0.1μF

AIN+

AIN–

4.7pF

2.2μF

4.7pF

4.7pF

VCM

ANALOGINPUT

0.1μF

0.1μF

T11:1

T1 = MA/COM ETC1-1-13.RESISTORS, CAPACITORSARE 0402 PACKAGE SIZE,EXCEPT 2.2F.

22032 F04

25Ω

25Ω

25Ω

10Ω

10Ω25Ω

LTC2203/LTC2202

Center-tapped transformers provide a convenient means of DC biasing the secondary; however, they often show poor balance at high input frequencies, resulting in large 2nd order harmonics.

Figure 4 shows transformer coupling using a transmis-sion line balun transformer. This type of transformer has much better high frequency response and balance than fl ux coupled center tap transformers. Coupling capacitors are added at the ground and input primary terminals to allow the secondary terminals to be biased at 1.25V.


LTC2203/LTC2202

2122032fd

Figure 5 demonstrates the use of an LTC1994 differential amplifi er to convert a single ended input signal into a differential input signal. The advantage of this method is that it provides low frequency input response; however, the limited gain bandwidth of any op amp will limit the SFDR at high input frequencies.

The internal programmable gain amplifi er provides the internal reference voltage for the ADC. This amplifi er has very stringent settling requirements and is not accessible for external use.

Figure 5. DC Coupled Input with Differential Amplifi er

VCM

22032 F05

–

–+

+CM LT1994

499Ω

100pF

100pF

100pF

2.2 μF

499Ω

523Ω 25Ω

25Ω499Ω

53.6Ω

AIN+

AIN–

LTC2203/LTC2202

Figure 6. Reference Circuit

PGA

1.25V

SENSE

VCMBUFFER

INTERNALADC

REFERENCE

RANGESELECT

AND GAINCONTROL

2.5VBANDGAP

REFERENCE

2.2μF

TIE TO VDD TO USE INTERNAL 2.5V

REFERENCEOR INPUT FOR

EXTERNAL 2.5V REFERENCE

OR INPUT FOR EXTERNAL 1.25V

REFERENCE

22032 F07

LTC2203/LTC2202

Figure 7. A 2.25V Range ADC with an External 2.5V Reference

VCM

SENSE

1.25V

3.3V

2.2μF

2.2μF1μF

22032 F08

LT1461-2.52 6

4

LTC2203/LTC2202

The SENSE pin can be driven ±5% around the nominal 2.5V or 1.25V external reference input. This adjustment range can be used to trim the ADC gain error or other system gain errors. When selecting the internal reference, the SENSE pin should be tied to VDD as close to the converter as possible. If the sense pin is driven externally it should be bypassed to ground as close to the device as possible with at least a 1μF ceramic capacitor.


The 25Ω resistors and 12pF capacitor on the analog inputs serve two purposes: isolating the drive circuitry from the sample-and-hold charging glitches and limiting the wideband noise at the converter input.

Reference Operation

Figure 6 shows the LTC2203/LTC2202 reference circuitry consisting of a 2.5V bandgap reference, a programmable gain amplifi er and control circuit. The LTC2203/LTC2202 has three modes of reference operation: Internal Refer-ence, 1.25V external reference or 2.5V external reference. To use the internal reference, tie the SENSE pin to VDD. To use the external reference, simply apply either a 1.25V or 2.5V reference voltage to the SENSE input pin. Both 1.25V and 2.5V applied to SENSE will result in a full scale range of 2.5VP-P (PGA = 0). A 1.25V output, VCM, is provided for a common mode bias for input drive circuitry. An external bypass capacitor is required for the VCM output. This provides a high frequency low impedance path to ground for internal and external circuitry. This is also the compensation capacitor for the reference; it will not be stable without this capacitor. The minimum value required for stability is 2.2μF.

LTC2203/LTC2202

2222032fd

In applications where jitter is critical, such as when digi-tizing high input frequencies, use as large an amplitude as possible. It is also helpful to drive the CLK pin with a low-jitter high frequency source which has been divided down to the appropriate sample rate. If the ADC is clocked with a sinusoidal signal, fi lter the CLK signal to reduce wideband noise and distortion products generated by the source.

Maximum and Minimum Conversion Rates

The maximum conversion rate for the LTC2203 is 25Msps. The maximum conversion rate for the LTC2202 is 10Msps. For the ADC to operate properly the CLK signal should have a 50% (±5%) duty cycle. Each half cycle must have at least 18.9ns for the LTC2203 internal circuitry to have enough settling time for proper operation. For the LTC2202, each half cycle must be at least 40ns.

An on-chip clock duty cycle stabilizer may be activated if the input clock does not have a 50% duty cycle. This circuit uses the falling edge of CLK pin to sample the analog input. The rising edge of CLK is ignored and an internal rising edge is generated by a phase-locked loop. The input clock duty cycle can vary from 30% to 70% and the clock duty cycle stabilizer will maintain a constant 50% internal duty cycle. If the clock is turned off for a long period of time, the duty cycle stabilizer circuit will require one hundred clock cycles for the PLL to lock onto the input clock. To use the clock duty cycle stabilizer, the MODE pin must be connected to 1/3VDD or 2/3VDD using external resistors.

The lower limit of the LTC2203/LTC2202 sample rate is determined by droop of the sample and hold circuits. The pipelined architecture of this ADC relies on storing analog signals on small valued capacitors. Junction leakage will discharge the capacitors. The specifi ed minimum operating frequency for the LTC2203/LTC2202 is 1Msps.

Figure 8. Sinusoidal Single-Ended CLK Drive

CLK0.1μF

0.1μF

4.7μF

1k

1k

FERRITEBEAD

CLEAN 3.3VSUPPLY

SINUSOIDALCLOCKINPUT

22032 F09

NC7SVU0456Ω

LTC2203/LTC2202

PGA Pin

The PGA pin selects between two gain settings for the ADC front-end. PGA = 0 selects an input range of 2.5VP-P; PGA = 1 selects an input range of 1.667VP-P. The 2.5V input range has the best SNR; however, the distortion will be higher for input frequencies above 100MHz. For applications with high input frequencies, the low input range will have improved distortion; however, the SNR will be 2.4dB worse. See the Typical Performance Characteristics section.

Driving the Clock Input

The CLK input can be driven directly with a CMOS or TTL level signal. A sinusoidal clock can also be used along with a low-jitter squaring circuit before the CLK pin (Figure 8).

The noise performance of the LTC2203/2202 can depend on the clock signal quality as much as on the analog input. Any noise present on the clock signal will result in additional aperture jitter that will be RMS summed with the inherent ADC aperture jitter.


LTC2203/LTC2202

2322032fd

Data Format

The LTC2203/LTC2202 parallel digital output can be selected for offset binary or 2’s complement format. The format is selected with the MODE pin. This pin has a four level logic input, centered at 0, 1/3VDD, 2/3VDD and VDD. An external resistor divider can be user to set the 1/3VDD and 2/3VDD logic levels. Table 1 shows the logic states for the MODE pin.

Table 1. MODE Pin Function

MODE OUTPUT FORMATCLOCK DUTY

CYCLE STABILIZER

0(GND) Offset Binary Off

1/3VDD Offset Binary On

2/3VDD 2’s Complement On

VDD 2’s Complement Off

Overfl ow Bit

An overfl ow output bit (OF) indicates when the converter is over-ranged or under-ranged. A logic high on the OF pin indicates an overfl ow or underfl ow.

Output Clock

The ADC has a delayed version of the CLK input available as a digital output. Both a noninverted version, CLKOUT+ and an inverted version CLKOUT– are provided. The CLKOUT+/CLKOUT– can be used to synchronize the converter data to the digital system. This is necesary when using a sinusoidal clock. Data can be latched on the rising edge of CLKOUT+ or the falling edge of CLKOUT–. CLKOUT+ falls and CLKOUT– rises as the data outputs are updated.

DIGITAL OUTPUTS

Digital Output Buffers

Figure 9 shows an equivalent circuit for a single output buffer in CMOS Mode. Each buffer is powered by OVDD and OGND, isolated from the ADC power and ground. The additional N-channel transistor in the output driver allows operation down to low voltages. The internal resistor in series with the output makes the output appear as 50Ω to external circuitry and eliminates the need for external damping resistors.

As with all high speed/high resolution converters, the digital output loading can affect the performance. The digital outputs of the LTC2203/LTC2202 should drive a minimum capacitive load to avoid possible interaction between the digital outputs and sensitive input circuitry. The output should be buffered with a device such as a ALVCH16373 CMOS latch. For full speed operation the capacitive load should be kept under 10pF. A resistor in series with the output may be used but is not required since the ADC has a series resistor of 43Ω on chip.

Lower OVDD voltages will also help reduce interference from the digital outputs.

22032 F10

OVDD

VDD VDD

0.1μF

TYPICALDATAOUTPUT

OGND

43Ω

OVDD 0.5VTO 3.6V

PREDRIVERLOGIC

DATAFROM

LATCH

LTC2203/LTC2202

Figure 9. Equivalent Circuit for a Digital Output Buffer


LTC2203/LTC2202

2422032fd

Digital Output Randomizer

Interference from the ADC digital outputs is sometimes unavoidable. Interference from the digital outputs may be from capacitive or inductive coupling or coupling through the ground plane. Even a tiny coupling factor can result in discernible unwanted tones in the ADC output spectrum. By randomizing the digital output before it is transmitted off chip, these unwanted tones can be randomized, trading a slight increase in the noise fl oor for a large reduction in unwanted tone amplitude.

•••

CLKOUT

OF

D15/D0

D14/D0

D2/D0

D1/D0

D0D0

D1

RAND = HIGH,SCRAMBLE

ENABLED

D2

D14

D15

OF

CLKOUT

RAND

22032 F11

LTC2203/LTC2202

Figure 10. Functional Equivalent of Digital Output Randomizer

The digital output is “Randomized” by applying an exclu-sive-OR logic operation between the LSB and all other data output bits. To decode, the reverse operation is applied; that is, an exclusive-OR operation is applied between the LSB and all other bits. The LSB, OF and CLKOUT output are not affected. The output Randomizer function is active when the RAND pin is high.


LTC2203/LTC2202

2522032fd

Figure 11. Descrambling a Scrambled Digital Output

•••

D1

D0

D2

D14

D15

PC BOARD

FPGA

CLKOUT

OF

D15/D0

D14/D0

D2/D0

D1/D0

D0

22032 F12

LTC2203/LTC2202

Output Driver Power

Separate output power and ground pins allow the output drivers to be isolated from the analog circuitry. The power supply for the digital output buffers, OVDD, should be tied to the same power supply as for the logic being driven. For example, if the converter is driving a DSP powered by a

1.8V supply, then OVDD should be tied to that same 1.8V supply. In CMOS mode OVDD can be powered with any logic voltage up to 3.6V. OGND can be powered with any voltage from ground up to 1V and must be less than OVDD. The logic outputs will swing between OGND and OVDD.


LTC2203/LTC2202

2622032fd

Figure 12. Functional Equivalent Block Diagram ofInternal Dither Circuit

S/HAMP

DIGITALSUMMATION

OUTPUTDRIVERS

MULTIBIT DEEPPSEUDO-RANDOM

NUMBERGENERATOR

16-BITPIPELINEDADC CORE

PRECISIONDAC

CLOCK/DUTYCYCLE

CONTROL

CLKOUT+

CLKOUT–

OFD15

•••

D0

CLK

DITHER ENABLEHIGH = DITHER ONLOW = DITHER OFF

DITH

ANALOG

AIN+

AIN–

INPUT

22032 F13

LTC2203/LTC2202

Internal Dither

The LTC2203/LTC2202 are 16-bit ADCs with very linear transfer functions; however, at low input levels even slight imperfections in the transfer function will result in unwanted tones. Small errors in the transfer function are usually a result of ADC element mismatches. An optional internal dither mode can be enabled to randomize the input’s location on the ADC transfer curve, resulting in improved SFDR for low signal levels.

As shown in Figure 12, the output of the sample-and-hold amplifi er is summed with the output of a dither DAC. The dither DAC is driven by a long sequence pseudo-random number generator; the random number fed to the dither DAC is also subtracted from the ADC result. If the dither DAC is precisely calibrated to the ADC, very little of the dither signal will be seen at the output. The dither signal that does leak through will appear as white noise. The dither DAC is calibrated to result in less than 0.5dB elevation in the noise fl oor of the ADC, as compared to the noise fl oor with dither off.

Grounding and Bypassing

The LTC2203/LTC2202 require a printed circuit board with aclean unbroken ground plane; a multilayer board with an internal ground plane is recommended. The pinout of the LTC2203/LTC2202 has been optimized for a fl owthrough layout so that the interaction between inputs and digital outputs is minimized. Layout for the printed circuit board should ensure that digital and analog signal lines are separated as much as possible. In particular, care should be taken not to run any digital track alongside an analog signal track or underneath the ADC.

High quality ceramic bypass capacitors should be used at the VDD, VCM, and OVDD pins. Bypass capacitors must be located as close to the pins as possible. The traces connecting the pins and bypass capacitors must be kept short and should be made as wide as possible.

The LTC2203/LTC2202 differential inputs should run parallel and close to each other. The input traces should be as short as possible to minimize capacitance and to minimize noise pickup.

Heat Transfer

Most of the heat generated by the LTC2203/LTC2202 is transferred from the die through the bottom-side exposed pad. For good electrical and thermal performance, the exposed pad must be soldered to a large grounded pad on the PC board. It is critical that the exposed pad and all ground pins are connected to a ground plane of suffi cient area with as many vias as possible.


LTC2203/LTC2202

2722032fd

9

20

20

8 7 6 5 4 3 2 1

A7

VC

C

U2

74V

CX

245B

QX

U1*

EX

PO

SED

PA

D

OV

P

OV

P

A6

A5

A4

A3

A2

A1

A0

B7

24

3

1

5 3

2

1

B6

B5

B4

B3

B2

B1

B0

10

9 8 7 6 5 4 3 2 1 10

11

12

13

14

15

16

17

18

19

11

12

13

14

15

16

17

18

19

GN

D

J13201S

-40G

1

U6

24LC

025

U5

NC

7S

V86P

5X

U4

NC

7S

V86P

5X

1

RN

1A

, 33

RN

1B

, 33

RN

1C

, 33

RN

1D

, 33

RN

2A

, 33

RN

2B

, 33

RN

2C

, 33

RN

2D

, 33

RN

3A

, 33

RN

3B

, 33

RN

3C

, 33

RN

3D

, 33

RN

4A

, 33

RN

4B

, 33

RN

4C

, 33

RN

4D

, 33

3 5 7 9 11

13

15

17

19

21

23

25

27

29

31

33

35

37

39

2 4 6 8

10

12

14

16

18

20

22

24

26

28

30

32

34

36

38

40

VC

C

U3

74V

CX

245B

QX

OV

P

8

1 2

7 6 5

1

5 3

4

2 3 4

VC

C

WP

SC

L

SD

A

A0

R17

10K

R18

10K

R19

10K

R5

33

A1

A2

A3

A7

A6

A5

A4

A3

A2

A1

A0

B7

B6

B5

B4

B3

B2

B1

B0

GN

D

OE

T/R

OE

T/R

OV

DD

D11

D10

D9

D8

OG

ND

CLK

OU

T +

CLK

OU

T – D7

D6

D5

OV

DD

SEN

SE

C1

0.1

μF

VC

M

VD

D

VD

D

GN

D

AIN

+

AIN

–

GN

D

GN

D/E

NC

+

GN

D/E

NC

–

GN

D

VD

D

1 2 3 4 5 6 7 8 9

10

11

12

36

35

34

33

32

31

30

29

28

27

26

25

GND

PGA

RAND

MODE

OE

OF

D15

D14

D13

D12

OGND

OVDD

13

14

15

16

17

18

19

20

21

22

23

24

49

48

47

46

45

44

43

42

41

40

39

38

37

VDD

VDD

GND

SHDN

DITH

D0

D1

D2

D3

D4

OGND

OVDD

JP6

DIT

H

VD

D

VD

D

VD

D

3

2

1

GN

D

JP6

DIT

H

VD

D

3

3

J3

1

24

R20

10k

R21

10k

2

1

GN

DC

19

0.1

μF

C14

0.1

μF

GND

C18

0.1

μF

C17

0.1

μF

C8

2.2

μF

C2

2.2

μF

C16

0.1

μF

C15

0.1

μF

C28

0.1

μF

C13

0.1

μF

OG

ND

1 2 3 4

8 71

6 5

VD

D

OV

P

OV

P

E3

E1

E4

U7

LT1763

R25

OU

T

AD

J

GN

D

VD

D+ 3

.3V

R29

1k

R30

OP

EN

R28

33

EN

CO

DE

INP

UT

GN

D

BY

P

IN

GN

D

GN

D

SHDN

C21

0.0

1μF

C22

1.0

μF

C20

10μF

6.3

V

C27

100μF

6.3

V O

PT

C23

4.7

μF

R23

100K

R22

105K

+

VD

D

OS

C1

OP

T.

VD

DV

DD

R33 *

EN

F O

GN

D

C9

0.1

μF

C3

8.2

pF

C5

8.2

pF

C7

8.2

pF

J4

J2

R12

OP

EN

R11

OP

EN

R24

OP

EN

R32

0

R27

10Ω

R8

51Ω

5.1

Ω

R10

5.1

ΩR

9O

PENR26

10Ω

1 2 3

5T1

AN

ALO

GIN

PU

T

DC

IN+

ETC

1-1

T

4

C4

C6

C26

0.1

μF

C25

0.1

μF

22

03

2 F

01

4

OP

EN

VD

D

JP2

SEN

SE

JP4

RA

ND

JP3

PG

A

VD

D

VD

D

R31

OV

DD

2

1

2

2

R6

OP

EN

R7

1K

R1

10K

R2

10K

R3

1K

R4

OP

EN

OV

PG

ND

33

GN

DG

ND

AS

SEM

BLY

TY

PE

* V

ER

SIO

N T

AB

LE

U1

R33

INP

UT F

REQ

UEN

CY

BIT

SM

SP

S

DC

919A

-ALT

C2207C

UK

0.0

1μF

DC

< A

IN <

70M

Hz

16

105

DC

919A

-BLT

C2206C

UK

0.0

1μF

DC

< A

IN <

70M

Hz

16

80

DC

919A

-CLT

C2205C

UK

0.0

1μF

DC

< A

IN <

70M

Hz

16

65

DC

919A

-DLT

C2204C

UK

0.0

1μF

DC

< A

IN <

70M

Hz

16

40

DC

919A

-ELT

C2203C

UK

0Ω

DC

< A

IN <

70M

Hz

16

25

DC

919A

-FLT

C2202C

UK

0Ω

DC

< A

IN <

70M

Hz

16

10

OP

EN

OP

EN

R13

OP

EN

Eval

uati

on C

ircu

it S

chem

atic

of

the

LTC

2203

/LTC

2202


LTC2203/LTC2202

2822032fd

Silkscreen Top

Silkscreen Topside


LTC2203/LTC2202

2922032fd

Inner Layer 2

Inner Layer 3


LTC2203/LTC2202

3022032fd

Silkscreen Bottom Side

Silkscreen Bottom


LTC2203/LTC2202

3122032fd

Information furnished by Linear Technology Corporation is believed to be accurate and reliable. However, no responsibility is assumed for its use. Linear Technology Corporation makes no representation that the interconnection of its circuits as described herein will not infringe on existing patent rights.

PACKAGE DESCRIPTIONUK Package

48-Lead Plastic QFN (7mm × 7mm)(Reference LTC DWG # 05-08-1704)

7.00 ± 0.10(4 SIDES)

NOTE:1. DRAWING CONFORMS TO JEDEC PACKAGE OUTLINE MO-220 VARIATION (WKKD-2)2. DRAWING NOT TO SCALE 3. ALL DIMENSIONS ARE IN MILLIMETERS4. DIMENSIONS OF EXPOSED PAD ON BOTTOM OF PACKAGE DO NOT INCLUDE MOLD FLASH. MOLD FLASH, IF PRESENT, SHALL NOT EXCEED 0.20mm ON ANY SIDE, IF PRESENT5. EXPOSED PAD SHALL BE SOLDER PLATED6. SHADED AREA IS ONLY A REFERENCE FOR PIN 1 LOCATION ON THE TOP AND BOTTOM OF PACKAGE

PIN 1 TOP MARK(SEE NOTE 6)

PIN 1CHAMFER

C = 0.35

0.40 ± 0.10

4847

1

2

BOTTOM VIEW—EXPOSED PAD

5.50 REF(4-SIDES)

0.75 ± 0.05 R = 0.115TYP

0.25 ± 0.05

0.50 BSC

0.200 REF

0.00 – 0.05

(UK48) QFN 0406 REV C

RECOMMENDED SOLDER PAD PITCH AND DIMENSIONSAPPLY SOLDER MASK TO AREAS THAT ARE NOT SOLDERED

0.70 ±0.05

5.50 REF(4 SIDES)

6.10 ±0.05 7.50 ±0.05

0.25 ±0.050.50 BSC

PACKAGE OUTLINE

5.15 ± 0.10

5.15 ± 0.10

5.15 ± 0.05

5.15 ± 0.05

R = 0.10TYP

LTC2203/LTC2202

3222032fd

Linear Technology Corporation1630 McCarthy Blvd., Milpitas, CA 95035-7417 (408) 432-1900 ● FAX: (408) 434-0507 ● www.linear.com © LINEAR TECHNOLOGY CORPORATION 2009

LT 0909 REV D • PRINTED IN USA

PART NUMBER DESCRIPTION COMMENTS

LTC1748 14-Bit, 80Msps ADC 76.3dB SNR, 90dB SFDR, 48-Pin TSSOP Package

LTC1750 14-Bit, 80Msps Wideband ADC Up to 500MHz IF Undersampling, 90dB SFDR

LT1993-2 High Speed Differential Op Amp 800MHz BW, 70dBc Distortion at 70MHz, 6dB Gain

LT1994 Low Noise, Low Distortion FullyDifferential Input/Output Amplifi er/Driver

Low Distortion: –94dBc at 1MHz

LTC2204 16-Bit, 40Msps, 3.3V ADC 480mW, 79.1dB SNR, 100dB SFDR, 48-Pin QFN

LTC2205 16-Bit, 65Msps, 3.3V ADC 610mW, 79dB SNR, 100dB SFDR, 48-Pin QFN



LTC2208 16-Bit, 130Msps, 3,3V ADC, LVDS Outputs 1250mW, 77.1dB SNR, 100dB SFDR, 64-Pin QFN

LTC2220-1 12-Bit, 185Msps, 3.3V ADC, LVDS Outputs 910mW, 67.7dB SNR, 80dB SFDR, 64-Pin QFN

LTC2224 12-Bit, 135Msps, 3.3V ADC, High IF Sampling 630mW, 67.6dB SNR, 84dB SFDR, 48-Pin QFN

LTC2242-12 12-Bit, 250Msps, 2.5V ADC, LVDS Outputs 740mW, 65.4dB SNR, 84dB SFDR, 64-Pin QFN

LTC2255 14-Bit, 125Msps, 3V ADC, Lowest Power 395mW, 72.5dB SNR, 88dB SFDR, 32-Pin QFN

LTC2284 14-Bit, Dual, 105Msps, 3V ADC, Low Crosstalk 540mW, 72.4dB SNR, 88dB SFDR, 64-pin QFN

LT5512 DC-3GHz High Signal LevelDownconverting Mixer

DC to 3GHz, 21dBm IIP3, Integrated LO Buffer

LT5514 Ultralow Distortion IF Amplifi er/ADC Driverwith Digitally Controlled Gain

450MHz to 1dB BW, 47dB OIP3, Digital Gain Control 10.5dB to 33dB in 1.5dB/Step

LT5515 1.5GHz to 2.5GHz Direct ConversionQuadrature Demodulator

High IIP3: 20dBm at 1.9GHz, Integrated LO Quadrature Generator

LT5516 800MHz to 1.5GHz Direct ConversionQuadrature Demodulator

High IIP3: 21.5dBm at 900MHz, Integrated LO Quadrature Generator

LT5517 40MHz to 900MHz Direct ConversionQuadrature Demodulator

High IIP3: 21dBm at 800MHz, Integrated LO Quadrature Generator

LT5522 600MHz to 2.7GHz High LinearityDownconverting Mixer

4.5V to 5.25V Supply, 25dBm IIP3 at 900MHz. NF = 12.5dB, 50Ω Single EndedRF and LO Ports

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