[ieee 2010 ieee international symposium on broadband multimedia systems and broadcasting (bmsb) -...
TRANSCRIPT
Abstract— It has been shown that quasi orthogonal space time
block codes (QOSTBC) can achieve high transmission rate with
partial diversity. Constellation rotational QOSTBC can achieve
full diversity. In this paper, we present a constellation rotational
QOSTBC concatenates Reed–Solomon (RS) error correction
code structure. At the receiver, pairwise detection and error
correction are first implemented. The decoded data are
regrouped. Parallel interference cancellation (PIC) and dual
orthogonal space time block code (OSTBC) decoding are
deployed to the regrouped data. The dual OSTBC decoding can
obtain better error performance than constellation rotational
QOSTBC. The pure concatenated scheme is shown to have
higher diversity order and have better error performance at
high signal-to-noise ratio (S*R) scenario than both QOSTBC
and OSTBC schemes. The PIC and dual OSTBC decoding
algorithm can further obtain approximate 1.0 dB gains than
pure concatenated scheme at 10-6 bit error probability (BEP).
The BEP performance of the proposed algorithm is very close to
that of dual OSTBC scheme with perfect interference
cancellation.
Index Terms—OSTBC, QOSTBC, Constellation Rotation, RS
Code, Parallel Interference Cancellation
I. INTRODUCTION
UASI-ORTHOGONAL space-time block codes
(QOSTBC) have recently become an attractive topic
because it can achieve high transmission rate compared to
orthogonal space-time block code (OSTBC) by scarifying
partial diversity [1]. The outage performance upper bound is
derived for QOSTBC in [2]. The maximum-likelihood (ML)
decoder works with pairwise symbols for QOSTBC, thus its
decoding complexity increases exponentially. A low
complexity sphere decoding algorithm was put forward to
decouple pairwise symbols decoding into single symbol
decoding in [3]. J. Kim et. al proposed another efficient
decoding algorithm based on iterative interference
cancellation [4]. Besides some low complexity decoding
algorithms [5, 6], many works have been done to achieve
higher transmission rate or higher diversity. An improved
QOSTBC design can guarantee both full diversity and fast
ML decoding by choosing half of the symbols from a signal
Z. H. Yan is a Ph. D student in Shanghai Jiao Tong University, China and
with College of Information Science and Engineering, Henan University of
Technology, China. (e-mail:[email protected])
Y. H. Yang is with the Electrical Engineering Department, Shanghai Jiao
Tong University, China.
Y. L. Lu and M. D. Ma are with the School of Electrical and Electronic
Engineering, Nanyang Technological University.
constellation set and the other half of them from a rotated
constellation set [7, 8]. Using channel correct code and
parallel interference cancellation (PIC) is another approach
to achieve high throughput and good performance with low
complexity detection and decoding algorithm [9]. However,
the PIC algorithm in [9] needs enough receive antennas at
receiver like in Bell Labs Layered Space-Time (BLAST)
and Generalized Layered Space-Time (GLST) architectures
[10, 11].
In this letter, we propose a new PIC different from [9] for
QOSTBC transmitting. There is no limits for receive
antennas number. The optimal constellation rotation is used
for QOSTBC. Forward error correction (FEC) code is
introduced at transmitter. At receiver, the pairwise joint
detection is first used in our new method. After the error
correction process by FEC, we reconstruct the transmitting
constellation symbols and divide them into two groups.
When one group of signals are removed from the received
signals, the system is equivalent to dual OSTBC systems.
Then, linear ML decoding can be processed for the dual
OSTBC systems. Full diversity gain and FEC code gain can
be simultaneously obtained. Reed–Solomon (RS) error
correction codes [12] are used as FEC codes in this paper. RS
codes were put forward by Irving Reed and Gus Solomon in
the journal of the society for industrial and applied
mathematics [13]. These codes have great power and utility,
and are today found in a wide variety of commercial
applications such as CD, DVD and WiMAX. By using
different constellation sizes and different RS code rate, the
system can allow for a flexible choice of transmission rates.
The dual OSTBC decoding can obtain more gain than the
QOSTBC with constellation rotation. Numerical results
show that the concatenated theme can achieve higher
diversity order than both QOSTBC and OSTBC for the same
transmission rate and total transmission power constraint. At
high signal noise ratio (SNR) scenario, the bit error
probability (BEP) performance of the concatenated scheme
is far better than that of QOSTBC and OSTBC. The
proposed PIC and dual OSTBC decoding algorithm can
achieve about 1.0 dB gains than the concatenated scheme
without using PIC algorithms at high SNR scenarios, too.
The BEP performance of the proposed algorithm is very
close to that of dual OSTBC scheme with perfect
interference cancellation.
The organization of the paper is as follows. Section 2
provides a QOSTBC concatenated with RS error correction
code scheme. Section 3 derives the PIC and dual OSTBC ML
decoding algorithm for the proposed scheme. Simulation
An Improved Decoding for Constellation Rotation QOSTBC
Concatenates RS Code Using Interference Cancellation
Zhenghang Yan, Yuhang Yang, Maode Ma, IEEE Member, and Yilong Lu, IEEE Member
Q
QOSTBC
Encoder
2M-ary Constellation
Mapper & Interleaving
.
.
. NT
1RS Encoder 1S/P
RS Encoder NT
.
.
.
User Data
.
.
.
.
.
.
(a) Transmitter: QOSTBC concatenated RS code structure
QOSTBCJoint
DeCoding
2M-ary ConstellationDeMapper &
DeInterleaving
.
.
.
NR
1
RS Error Correct 1. . .
RS Error Correct NT
Regroup
PIC
PICDual OSTBC ML Decoding
Dual OSTBC ML Decoding
P/S
Output Data
.
.
.
...
(b) Receiver: PIC and dual OSTBC decoding
Fig. 1. Transmitter and receiver structures
results are presented in section 4 and conclusions are
summarized in section 5.
II. THE CONCATENATED QOSTBC SCHEME
We focus on the widely used QOSTBC scheme in [1] for
systems with four transmit antennas and nR receive antennas.
Analysis for other QOSTBCs and any transmit/receive
antennas is similar. Quasi-stationary flat Rayleigh fading
channel is assumed and ideal channel state information (CSI)
is available at the receiver. The proposed concatenated
QOSTBC structure is shown in Fig. 1a. Considering a 2M
-ary
constellation, the input data stream is demultiplexed into M
data substreams in series/parallel (S/P) convertor. Each
substream is encoded using a RS code respectively. The ith
bits
from all M RS codewords collectively select the ith
2M
-ary
constellation point si. Every 4L constellation symbols
compose one frame. After all 4L constellations symbols have
been decided in a frame, we take the lth
, the (l+L)th
, the
(l+2L)th
and the (l+3L)th
symbols (l=1,…,L) as a group and
denote them as x1(l), x2(l), x3(l), x4(l). Then, the QOSTBC
codewords transmitted at the lth
time slot are expressed as [1]
* *
1 2 3 4
* *12 34 2 1 4 3
* * * *34 12 3 4 1 2
* *
4 3 2 1
- -
- -
- -
T
x x x x
x x x x
x x x x
x x x x
= = −
A AΑ
A A
(1)
where * is conjugate operation and
* *
m n
mn
n m
x x
x x
= −
A (2)
The index l is ignored for simplify. For the elements in (1), x1
and x2 are selected from the constellation space А, x3 and x4
are selected from the constellation space ejθА. We call the
constellation space ejθA as space B. Let the total transmitted
energy across all nT transmit antennas be 1 for each time slot.
The received signal at the nR receive antennas is
TY = HΑ + * (3)
where received signal Y is an �R×4 matrix. The element
hij of the �R�T channel matrix H is the total channel
gain from the jth
transmit antenna to the ith
receive
antenna. * is an �R×4 noise matrix whose entries are
i.i.d complex Gaussian noise with mean 0 and variance σ2
n , and independent over time slots.
III. DETECTION AND DECODING
At the receiver, QOSTBC pairwise ML joint detection is first
applied to the received signals as shown in Fig. 1b. By
minimizing f14(x1, x4) the transmitted symbols x1 and x4 can be
decoded pairwise and the transmitted symbols x2 and x3 can be
decoded pairwise by minimizing f23(x2, x3) as [1, 7].
{ }
( ){(( )( ) }
1 4
1 4
1 1
1 4 14 1 4,
* * * *
1 1 2 2 3 3 4 4 1,
1
* * * *
4 1 3 2 2 3 1 4 4
2 2* * * * *
1 4 2 3 2 3 1 4 1 4 1 4
, min ( , )
min 2 Re
R
x x
�
m m m m m m m mx x
m
m m m m m m m m
m m m m m m m m F
x x f x x
h y h y h y h y x
h y h y h y h y x
h h h h h h h h x x x x
∈ ∈
∈ ∈=
=
= − − − −
+ − + + −
+ − − + + +
∑
Α B
Α B
H ( ))}2
(4)
and
{ }
( ){(( )( ) }
2 3
2 3
1 1
2 3 23 2 3,
* * * *
2 1 1 2 4 3 3 4 2,
1
* * * *
3 1 4 2 1 3 2 4 3
2* * * * *
2 3 1 4 1 4 2 3 2 3
, min ( , )
min 2 Re
R
x x
�
m m m m m m m mx x
m
m m m m m m m m
m m m m m m m m F
x x f x x
h y h y h y h y x
h y h y h y h y x
h h h h h h h h x x
∈ ∈
∈ ∈=
=
= − + − +
+ − − + +
+ − − + +
∑
Α B
Α B
H ( ))}2 2
2 3x x+
(5)
The simplified ML decoding algorithms in [3, 4] can be used
in place of the algorithm in [1] in order to reduce computation
complexity. After joint detection, 2M
-ary constellation
de-mapping, de-interleaving and RS error correction are
operated to the decoded data in a frame. After error correction
is completed, we take interleaving and 2M
-ary constellation
mapping process to the corrected data frame in the same way
as the process in the transmitting process and get x1
1 , x1
2 , x1
3 and
x1
4 , where superscript 1 denotes the 1th
iterative. The symbols x1
3 and x1
4 are input to a PIC module and the symbols x1
1 and x1
2
are input to another PIC module. At the first PIC module, we
remove x1
3 and x1
4 from the received signals by
1* 1
3 4
1* 1
4 31
12 1 1*
3 4
1 1*
4 3
0 0 -
0 0 - -
- 0 0
0 0
x x
x x
x x
x x
= −
Y Y H (6)
The subscript of Y1
12 indicates that the signals Y1
12 are
contributed by x1 and x2. The superscript of Y1
12 indicates
iterative number. Assuming x1
3 and x1
4 are successfully
decoded (x3= x1
3 and x4= x1
4 ), then
*
1 2
*
2 11
12 *
1 2
*
2 1
- 0 0
0 0
0 0 -
0 0
x x
x x
x x
x x
= +
Y H * (7-1)
or
5 10 15 20 25 30 3510
-6
10-5
10-4
10-3
10-2
10-1
SNR (dB)
Bit Error Porbability
2 bits/s/Hz
Uncoded
OSTBC
QOSTBC
Rotation QOSTBC
Rot QOSTBC + RS
Rot QOSTBC+RS+PIC
RS+PIC Bound
Fig. 2. Bit-error probability versus SNR for all transmission schemes at 2 bits/sec/Hz; 4 transmit antennas, 1 receive antenna
[ ] [ ]* *
1 2 1 21
12 3 4* *
2 1 2 1
- -
x x x x
x x x x
= +
1 2Y h h h h * (7-2)
where hi is the ith
column vector of channel matrix H.
Obviously, there are two independent OSTBC received
signals in (7-2). We derive the decision metric
2*
1 2
*
2 11
12 *
1 2
*
2 1
- 0 0
0 0
0 0 -
0 0 F
s s
s s
s s
s s
−
Y H (8)
where ||.||2
F is squared Frobenius norm, s1 and s2 are all possible
transmitting constellation symbols. Minimizing the decision
metric results in a ML decoding. We expand the above metric
and get two independent parts, one of which is only a function
of s1 and the other one is only a function of s2. Thus, after
some manipulation x1 can be detected by minimizing the
decision metric
( ) ( )( )
( ) ( )( )
2
1 * 1 * *
12 3 12 4 1
1
24
2 21 * 1 *
12 1 12 2 1 1
1 1 1
,3 ,4
,1 ,2 2
R
R R
�
j j
j
� �
j j ji
j j i
y j h y j h s
y j h y j h s h s
=
= = =
+ − +
+ − + − +
∑
∑ ∑∑
(9)
and x2 can be detected by minimizing the decision metric
( ) ( )( )
( ) ( )( )
2
1 * 1 * *
12 4 12 3 2
1
24
2 21 * 1 *
12 2 12 1 2 2
1 1 1
,3 ,4
,1 ,2 2
R
R R
�
j j
j
� �
j j ji
j j i
y j h y j h s
y j h y j h s h s
=
= = =
− − +
− − + − +
∑
∑ ∑∑
(10)
where y1
12(j,i) is the jth
row, the ith
column element of Y1
12. It is
shown that x1 and x2 can be solely detected with linear ML
decoding algorithm respectively. At high SNR, the error
performance of dual OSTBC decoding is superior to that of
the QOSTBC with constellation rotation because the
interference is cancelled from the received signals.
Comparing with pariwise detection, the increased
computation of solely detection is also accepted. Similarly,
x3 and x4 can be detected in the same way in another PIC and
dual OSTBC ML decoding branch.
The detected x1, x2, x3 and x4 are input to 2M
-ary
constellation de-mapper and are dealt with the same process
after QOSTBC joint detection. The user data can be obtained
at the output of parallel/serial convertor. Furthermore, the
PIC and dual OSTBC decoding process can be iteratively
implemented after x1, x2, x3 and x4 are all decoded as shown
in Fig.1b.
IV. NUMERICAL RESULTS
In this section, we provide simulation results for the
proposed PIC and dual OSTBC decoding algorithm and
compare it with the results for other transmitter/receiver
schemes. In all simulations, four transmit antennas and one
receive antenna are deployed similarly as in [1]. The total
average transmission power keeps constant for all schemes.
Fig.2 provides simulation results for the transmission rate of
2 bits/s/Hz. In order to keep the same transmission rate, we
used appropriate constellation size for different transmission
schemes. QPSK is used for uncoded scheme and rate one
QOSTBC. 16-QAM is adopted for the proposed concatenated
scheme and rate ½ OSTBC. The optimal rotation angle θ=π/4
is adopted for constellation rotation QOSTBC with QPSK and
16-QAM modulation [8]. There is no rate ½ RS code, thus we
obtain rate ½ by using three 7/15 RS code blocks and one 9/15
BCH code block as one transmission unit.
The slope of the BEP-SNR curve dictates the degree of
diversity. Constellation rotation QOSTBC achieves as full
diversity as OSTBC and its error performance is superior to
OSTBC and QOSTBC. Fig.2 shows that the scheme using
QOSTBC concatenated RS code has higher diversity order
than full diversity order because FEC code gains are
introduced. At very low SNR, concatenated scheme has bad
error performance because large constellation size is adopted.
The error performance of the concatenated scheme is better
than constellation rotation QOSTBC when SNR>16.3 dB and
obtains 3.5 dB gain at 10-6
BEP. The proposed PIC and dual
OSTBC decoding scheme can achieve full diversity order and
FEC code gain simultaneously. Comparing with pure
concatenated scheme, the proposed PIC algorithm only
obtains a little gain at very low SNR scenario. The reason lies
in that in some frames decoding errors are beyond the
correction capability of RS code and more errors are incurred
after error correction process on the contrary. The proposed
PIC scheme can obtain obvious gain than pure concatenated
scheme except at very low SNR scenario. For example, 1.0 dB
gains are obtained at 10-6
BEP. The performance upper bound
of the proposed PIC scheme is also described in Fig.2. It is
assumed that perfect PIC is implemented for performance
upper bound. The distance between performance upper bound
and BER curve of the proposed PIC scheme is about 0.4 dB. It
is introduced by decoding errors at pairwise ML decoding and
error propagation in PIC process. Numerical outcome shows
that no gain is obtained at the second iterative PIC process and
the BEP curve of the second iterative PIC process is ignored
in this paper. It is because RS code is a kind of block code and
iterative decoding can not improve the performance of block
code.
V. CONCLUSIONS
We have deployed a constellation rotational QOSTBC
concatenated RS error correction code structure at the
transmitter. At the receiver, after pairewise ML detection and
error correction, the proposed PIC and dual OSTBC detection
are used. In the proposed PIC scheme, rate one is fulfilled for
QOSTBC. Full diversity is achieved by dual OSTBC ML
decoding after PIC is implemented. Code gain is obtained by
using RS error correction code. Thus, full transmitting rate,
full diversity and FEC code gain can be obtained
simultaneously. The constellation rotational QOSTBC
concatenated RS code structure have better BEP performance
than QOSTBC and OSTBC schemes except at very low SNR
scenario. The proposed PIC and dual OSTBC decoding
algorithm for the concatenation scheme can provide about 1.0
dB performance gains at 10-6
BEP. After PIC and dual
OSTBC ML decoding, the BEP performance of the
concatenated QOSTBC scheme is very close to that of dual
OSTBC scheme.
ACKNOWLEDGMENT
The authors would like appreciate Chinese Scholarship
Council for the financial support.
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