concept kit:pwm boost converter transients model
DESCRIPTION
Concept Kit:PWM Boost Converter Transients ModelTRANSCRIPT
Concept Kit:PWM Boost Converter
Transients Model
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 1
Power Switches(Semiconductor)
Filter & LoadPWM IC (Voltage Mode)
VREF
+-
VOUTL1 2
C
Rload
Vo
ESROSC
REF
E / A
Comp
+
-
-
+
U?PWM_IC
FOSC = 52K
VP = 2.5VREF = 1.23
pwm
+ -
+ - S1S
RON = 100m
D1DIODE
Contents
1. The PWM Boost Converter Topology
2. Power Switches (Semiconductor)
3. Boost Converter Design Workflow
Setting PWM Controller’s Parameters
Setting Output Voltage: Rupper, Rlower
Inductor Selection: L
Capacitor Selection: C, ESR
Setting the Compensator Parameters
4. Boost Converter Simulation (Example)
4.1 Switching Waveforms
4.2 Power State Switches Voltage and Current
5. Load Transient Response Simulation (Example)
6. Boost Converter Reliability Testing (Example)
7. Converter Efficiency
7.1 Converter Efficiency vs. MOSFET, Rds(on)
7.2 Converter Efficiency vs. DIODE, VF
8. Simulation Using Real Device Models (Example)
8.1 Switching Waveforms (Real Device Models)
8.2 Converter Efficiency (Real Device Models)
9. SpicePark of MOSFET Model
Simulation Index
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 2
1
2
3
4
5
C
D1DIODE
+
-
+
-
S1 S
RON = 0.01R
v out
pwm
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = {f osc}
VP = {Vp}VREF = {Vref }
C1
C2
R1R2
C3
RLs
Rlower
Vin
ESR
Rupper
L
0
0
err
1.The PWM Boost Converter Topology
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 3
Power Stage: Boost topology
Error Amplifier
Type 3 Compensator*
* Please see appendix B for the detailVoltage Mode
D
BOOST_SW
D
VIN
+
-
VOUT
+
-
IIN IOUT• A Near-Ideal DIODE can be modeled by
using SPICE primitive model (D), which
parameters are : N=0.01 RS=0 CJO=1p.
• A near-ideal MOSFET can be modeled by using PSpice VSWITCH that is voltage
controlled switch. (the default parameters are Roff=1e7 Ron=0.01 Voff=1.47V
Von=1.5V)
D1DIODE
+
-
+
-
S1 S
RON = 0.01
pwm
2.Power Switches (Semiconductor)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 4
(MOSFET)
The parameter RON represents Rds(on) characteristics of MOSFET (usually provide by the manufacturer datasheet).
D
BOOST_SW
D
VIN
+
-
VOUT
+
-
IIN IOUT
D
BOOST_SW
D
VIN
+
-
VOUT
+
-
IIN IOUT
D
BOOST_SW
D
VIN
+
-
VOUT
+
-
IIN IOUT
3.Boost Convertor Design Workflow
The Purpose of the Circuit Simulation
• To Evaluate and Verify the Design of the PWM Boost Converter.
• To Optimize the Parameters of the PWM Boost Converter.
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 5
Setting PWM Controller’s Parameters: FOSC , VREF, VP1
Setting Output Voltage: Rupper, Rlower2
Inductor Selection: L3
Capacitor Selection: C, ESR4
Setting the Compensator Parameters: R2, C1, C25
Continue next slide
Boost Convertor Design Workflow
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 6
Evaluations:
• Switching Waveforms,
• Power State Switches Voltage and Current,
• Load Step Transient Response,
• and so on
Reliability: L sweep (example)
Evaluations:
• Converter Efficiency vs. MOSFET, Rds(on)
• Converter Efficiency vs. Diode, VF
Evaluations Using Real Device Models (as an Option)
C
D1DIODE
+
-
+
-
S1 S
RON = 0.01R
pwm
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = {f osc}
VP = {Vp}VREF = {Vref }
C1
C2
R1 R2
C3
RLs
Rlower
Vin
ESR
Rupper
L
0
0
err
v out
Boost Convertor Design Workflow
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 7
1
2
3
4
5
Type 3 Compensator*
5
Voltage Mode
Design Specification (Example)
A boost converter is designed to deliver 12V, 1.5A from a 3.3 V battery
Step-Up (Boost) Converter :
• Vin,max = 3.63 (V)
• Vin,min = 2.97 (V)
• Vout = 12 (V)
• Vout, ripple = 180mVP-P (1.2%)
• Io,max = 1.5 (A)
• Io,min = 0.2 (A)
Control IC :
• Part # TPS43000 (PWM Controller IC)
• Switching Frequency – fosc = 300 (kHz)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 8
Vin = 3.310%
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = 300K
VP = 2.2VREF = 0.8
Setting PWM Controller’s Parameters
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 9
comp
PWM
FB
1
• FOSC, Oscillation frequency (frequency of the
sawtooth signal).
• VREF, feedback reference voltage, value is
given by the datasheet
• VP = the sawtooth peak voltage.
• If VP does not provided, it could be calculated from:
VP = VFB /d
VFB = VFBH – vFBL
d = dMAX – dMIN
where
vFBH is maximum FB voltage where d = 0
vFBL is minimum FB voltage where d =1(100%)
dMAX is maximum duty cycle, e.g. d = 0(0%)
dMIN is minimum duty cycle, e.g. d =1(100%)
The Comparator compares the error voltage
(between FB and REF) with a sawtooth signal
(frequency = FOSC, peak saw voltage =
VP) to generate PWM signal, as shown in the
figure below.
Time
V(PWM)
V(osc) V(comp)
0V
2.0V
3.0V
SEL>>VP
Duty cycle (d) is a value from 0 to 1
f = FOSC
If vFBH and vFBL are not provided, the default value, VP=2 could be used.
(eq.1)
Setting PWM Controller’s Parameters (Example)
So we’ve got
VREF = 0.8
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 10
The VREF value is given by the datasheet
TPS43000 electrical characteristics
1
The switching frequency 300kHz constant is chosen
Input
FOSC = 300k
Setting PWM Controller’s Parameters (Example)
from the (eq.1)
VP = VFB /d
• from the datasheet , VFB = (2-0) = 2V, and d = (0.9-0) = 0.9
VP = 2 / 0.9
= 2.2
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 11
The VP ( sawtooth signal amplitude ) can be calculated from the characteristics below.
TPS43000 electrical characteristics
1
• Use the following formula to select the resistor values.
Example
Given: Vout = 12V
Vref = 0.8
Rlower = 10k
then:
Rupper = 140k
Setting Output Voltage: Rupper, Rlower
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 12
lower
upperREFOUT
R
RVV 1
2
REF
lowerREFOUTupper
V
RVVR
)(
(eq.2)
Inductor Selection: L, RLS
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 13
Inductor Value
• The output inductor value is selected to set the
converter to work in CCM (Continuous Current
Mode) for all load current conditions.
• Calculated by
• with
Where
• LCCM is the inductor that make the converter to work in CCM.
• Dmin is the minimum duty cycle; Dmin =1- Vin,max /VOUT
• Dmax is the maximum duty cycle; Dmax =1- Vin,min /VOUT
• RLs is load resistance at the minimum output current ( Io,min )
• fosc is switching frequency
• IL is inductor ripple current
min,
2minmin
2
)1(
Oosc
OUTCCM
If
VDDL
3
osc
inL
fL
DVI
maxmin,
C
D1DIODE
+
-
+
-
S1 S
RON = 0.01R
pwm
RLs
ESR
L
(eq.3)
(eq.4)
Inductor Selection: L, RLS (Example)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 14
Inductor Value
from (eq.3)
Given:
• Vin,max = 3.63V (3.3V+10%), Vout = 12V, Io,min = 0.2A
• Dmin = 1- Vin,max /Vout = 0.7
• fosc = 300kHz
Then:
• LCCM 6.4 (uH),
• L = 6.8 (uH) is selected
3
min,
2minmin
2
)1(
Oosc
OUTCCM
If
VDDL
C
D1DIODE
+
-
+
-
S1 S
RON = 0.01R
pwm
RLs
ESR
L
Capacitor Selection: C, ESR
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 15
Capacitor Value
• The minimum allowable output capacitor
value should be determined by
• In addition, the capacitor must be able to handle the current more than
• The ESR of the output capacitor adds some more ripple, so it should be limited by
following equation:
OSCrippleout
o
fV
IDC
,
max,max
C
rippleout
I
VESR
,
4
2,
LRatedC
II
• Where IL is calculated by the (eq.4)
(eq.5)
(eq.6)
(eq.7)
C
D1DIODE
+
-
+
-
S1 S
RON = 0.01R
pwm
RLs
ESR
L
Capacitor Selection: C, ESR (Example)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 16
Capacitor Value
From the (eq.5)
and the (eq.6) and (eq.7)
Given:
• Dmax = 0.75 V
• Io, max = 1.5 A
• Vout,ripple = 0.18 V
Then:
• C 20.9 (F)
In addition:
• IC,Rated ≈ 550mA ESR 27m
C
rippleout
I
VESR
,
4
OSCRippleout
o
fV
IDC
,
max,max
2
LC
II
C
D1DIODE
+
-
+
-
S1 S
RON = 0.01R
pwm
RLs
ESR
L
C
D1DIODE
+
-
+
-
S1 S
RON = 0.01R
pwm
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = {f osc}
VP = {Vp}VREF = {Vref }
Type 3 Compensator v out
C1
C2
R1R2
C3
RLs
Rlower
Vin
ESR
Rupper
L
0
0
err
• Loop gain for this configuration is
• The purpose of the compensator G(s)
is to tailor the converter loop gain
(frequency response) to make it stable
when operated in closed-loop
conditions.
• The element of the Type 3 compensator (C1, C2 , C3 , R1, and R2 ) can be extracted
by using Boost_Calculator.xls (Excel sheet) and open-loop simulation with the
Average Models (ac models).
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 17
PWMGsGsHsT )()()(
GPWM
Compensator: G(s)
Power stage: H(s)
Stabilizing the Converter5
Remark: The Average Models are not included with this package.
Specification:
VIN = 3.3V 10%
VOUT = 12V
IOUT = 0.2 ~ 1.5A
PWM Controller:
fOSC = 300kHz
VREF = 0.8V
VP1 = 2.2V
Rlower = 10k,
Rupper = 140k,
L = 6.8uH (RLS=10m ),
C = 1410uF (ESR = 27m),
Task:
•Voltage and Current Waveforms Evaluation.
4.Boost Converter Simulation (Example)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 18
Characteristics from Texas Instruments IC: TPS43000.
2
*Analysis directives:
.TRAN 0 10ms 0ms 100n
.OPTIONS ABSTOL= 1.0n
.OPTIONS CHGTOL= 0.01u
.OPTIONS ITL1= 200
.OPTIONS ITL2= 100
.OPTIONS ITL4= 50
.OPTIONS RELTOL= 0.01
D1DIODE
+
-
+
-
S1 S
RON = 0.01
pwm
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = 300k
VP = 2.2VREF = 0.8
C1
8.259n
C2795p
R1
47.9k
R24.9k
C3
2.826nF
RLs10m
v out
Rlower10k
Vin
3.3
ESR
27m
C
1410u
Rupper140k
L6.8u
0
0
err
R
12
• The simulation results shows waveforms of the boost converter.
• Output ripple voltage (caused by ESR) = 116mVP-P.
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 19
Control Voltage
V(PWM)
VOUT, RIPPLE
Inductor Current
I(L)
Switch Current
ID(S1)
Time
9.980ms 9.984ms 9.988ms 9.992ms 9.996ms 10.000ms
v(vout)
11.8V
12.0V
12.1V
12.2V
SEL>>(9.986m,11.970)
(9.982m,12.086)
I(L)
0A
2.5A
5.0A
I(S1:3)
0A
2.5A
5.0A
v(pwm)
0V
5.0V
4.1 Switching Waveforms
Time
9.990ms 9.992ms 9.994ms 9.996ms 9.998ms 10.000ms
1 V(D1:A,D1:C) 2 I(D1)
-16V
-8V
0V
8V
16V1
>>
-5.0A
-2.5A
0A
2.5A
5.0A2
(9.996m,4.3554)
(9.993m,-11.940)
1 V(S1:3,S1:4) 2 I(S1:3)
0V
4V
8V
12V
16V1
SEL>>
0A
1.5A
3.0A
4.5A
6.0A2
SEL>>
(9.996m,4.3125)(9.992m,12.095)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 20
4.2 Power State Switches Voltage and Current
• Switch (MOSFET) has the steady state voltage: VDS, PEAK = 12.095V and
current: ID, PEAK = 4.312A
• Diode has the steady state voltage: VAK, PEAK = -11.940V and current: IF, PEAK
= 4.355A
SW (MOSFET) Voltage VDS
SW (MOSFET) Current ID
Diode Voltage VAK
Diode Forward Current IF
D1DIODE
+
-
+
-
S1 S
RON = 0.01
pwm
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = 300k
VP = 2.2VREF = 0.8
C1
8.259n
C2795p
R1
47.9k
R24.9k
C3
2.826nF
RLs10m
v out
Rlower10k
Vin
3.3
ESR
27m
C
1410u
Rupper140k
L6.8u
0
0
err
I1
TD = 19m
TF = 10uPW = 2mPER = 1
I1 = 0.2I2 = 1.5
TR = 10u
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 21
The converter are connected with step-load to perform load transient response simulation.
*Analysis directives:
.TRAN 0 26ms 18ms 100n
.OPTIONS ABSTOL= 1.0n
.OPTIONS CHGTOL= 0.01u
.OPTIONS ITL1= 200
.OPTIONS ITL2= 100
.OPTIONS ITL4= 50
.OPTIONS RELTOL= 0.01
Iload = 0.2A step to 1.5A
5.Load Transient Response Simulation (Example)
Time
18ms 20ms 22ms 24ms 26ms
v(vout)
11.8V
11.9V
12.0V
12.1V
12.2V
SEL>>
(21.022m,12.162)
(19.099m,11.912)
I(I1)
0A
0.4A
0.8A
1.2A
1.6A
2.0A
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 22
5.Load Transient Response Simulation (Example)
• The simulation results shows output voltage change waveforms caused by
step load current.
0.2-1.5A Step load current
Output Voltage Change
D1DIODE
+
-
+
-
S1 S
RON = 0.01
pwm
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = 300k
VP = 2.2VREF = 0.8
C1
8.259n
C2795p
R1
47.9k
R24.9k
C3
2.826nF
RLs10m
v out
Rlower10k
Vin
3.3
ESR
27m
C
1410u
Rupper140k
0
L{L}
0
err
R
60
PARAMETERS:
L = 6.8u
Specification:
VIN = 3.3V 10%
VOUT = 12V
IOUT = 0.2 ~ 1.5A
PWM Controller:
fOSC = 300kHz
VREF = 0.8V
VP1 = 2.2V
Rlower = 10k,
Rupper = 140k,
L = Swept parameter (RLS=10m ),
C = 1410uF (ESR = 27m),
Task:
•To check that the converter still work in CCM
after 15% reduction of the inductor value.
6.Boost Converter Reliability Testing (Example)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 23
2
*Analysis directives:
.TRAN 0 20ms 0 100n
.STEP PARAM L LIST 6.8u, 5.78u
.OPTIONS ABSTOL= 1.0n
.OPTIONS CHGTOL= 0.01u
.OPTIONS ITL1= 200
.OPTIONS ITL2= 100
.OPTIONS ITL4= 50
.OPTIONS RELTOL= 0.01
Iload, min
= 0.2A
Time
19.990ms 19.992ms 19.994ms 19.996ms 19.998ms 20.000ms
v(vout)
12.04V
11.98V
SEL>>
I(L)
0A
0.8A
1.6A
I(S1:3)
0A
1.0A
2.0A
v(pwm)
0V
5.0V
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 24
6.Boost Converter Reliability Testing (Example)
• The simulation results shows waveforms of the converter at L=6.8uH and 5.78uH
• At L = 5.78uH(-15%), the converter still work in CCM
A: V(PWM),
D: VOUT, RIPPLE
C: I(L)
B: ID(S1)
the converter works in CCM (no zero current) at L=5.78uH.
L=6.8uH
L=5.78uH
D1DIODE
+
-
+
-
S1 S
RON = {Rdson}
pwm
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = 300k
VP = 2.2VREF = 0.8
C1
8.259n
C2795p
R1
47.9k
R24.9k
C3
2.826nF
RLs10m
v out
Rlower10k
Vin
3.3
ESR
27m
C
1410u
Rupper140k
L6.8u
0
0
err
R
12
PARAMETERS:
Rdson = 0.1
7.1 Converter Efficiency vs. MOSFET Rds(on)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 25
Perform transient simulation to measure the converter efficiency at Rds(on)= 0.01 and 0.1 .
*Analysis directives:
.TRAN 0 20ms 18.8m 100n
.STEP PARAM Rdson LIST 0.01, 0.1
.OPTIONS ABSTOL= 1.0n
.OPTIONS CHGTOL= 0.01u
.OPTIONS ITL1= 200
.OPTIONS ITL2= 100
.OPTIONS ITL4= 50
.OPTIONS RELTOL= 0.01
Time
19.50ms 19.55ms 19.60ms 19.65ms 19.70ms 19.75ms 19.80ms 19.85ms 19.90ms 19.95ms
100*AVG(W(R))/AVG(-W(Vin))
50
60
70
80
90
100
(19.750m,88.600)
(19.750m,97.343)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 26
7.1 Converter Efficiency vs. MOSFET Rds(on)
• The converter efficiency is decreased from 97.3% to 88.6% when
Rds(on) increase from 0.01 to 0.1.
Efficiency (%)
Rds(on) = 0.01, Efficiency = 97.3 %
Rds(on) = 0.1, Efficiency = 88.6 %
Rds(on) = 0.01
Rds(on) = 0.1
D1DIODE
+
-
+
-
S1 S
RON = 0.01
pwm
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = 300k
VP = 2.2VREF = 0.8
C1
8.259n
C2795p
R1
47.9k
R24.9k
C3
2.826nF
RLs10m
v out
Rlower10k
Vin
3.3
ESR
27m
C
1410u
Rupper140k
0
L6.8u
0
err
R
12
PARAMETERS:
N = 0.01
7.2 Converter Efficiency vs. Diode, VF
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 27
Perform transient simulation to measure the converter efficiency at DIODE (N) = 0.01 and 0.4
V_V1
0V 0.12V 0.24V 0.36V 0.48V 0.60V 0.72V 0.84V 0.96V 1.08V
I(D1)
0A
0.1A
0.2A
0.3A
0.4A
0.5A
0.6A
0.7A
0.8A
0.9A
1.0A
VF increases when DIODE (N) increases.
VF
Diode Forward I – V Characteristics
Diode Forward Voltage vs. Diode model parameter: N
*Analysis directives:
.TRAN 0 20ms 18.8m 100n
.STEP PARAM N LIST 0.01, 0.4
.OPTIONS ABSTOL= 1.0n
.OPTIONS CHGTOL= 0.01u
.OPTIONS ITL1= 200
.OPTIONS ITL2= 100
.OPTIONS ITL4= 50
.OPTIONS RELTOL= 0.01
Time
19.50ms 19.55ms 19.60ms 19.65ms 19.70ms 19.75ms 19.80ms 19.85ms 19.90ms 19.95ms
100*AVG(W(R))/AVG(-W(Vin))
50
60
70
80
90
100
(19.750m,94.663)
(19.750m,97.343)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 28
7.2 Converter Efficiency vs. Diode, VF
Efficiency (%)
DIODE (N) = 0.01, Efficiency = 97.3 %
DIODE (N) = 0.4, Efficiency = 94.6 %
• The converter efficiency is decreased from 97.3% to 94.7% when
DIODE’s parameter N increase from 0.01 to 0.4
pwm
OSCREF
E / A
Comp
+
-
-
+
U1PWM_IC
FOSC = 300k
VP = 2.2VREF = 0.8
C1
8.259n
C2795p
R1
47.9k
R24.9k
C3
2.826nF
RLs10m
v out
Rlower10k
Vin
3.3
ESR
27m
C
1410u
Rupper140k
0
L6.8u
0
err
R
12
U2TPC6005S
D1
M2FM3
8.Simulation Using Real Device Models (Example)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 29
As we can see in the efficiency simulation (topic #7) that’s how the switching devices effect
the simulation result. For the accurate simulation result, the accurate models, that relate to
the real devices characteristics, are needed.
The Real Device Models of MOSFET (Toshiba N Channel MOS Part# TPCP6005)
The Real Device Models of Schottky Diode (Shindengen SBD Part# M2FM3)
• The real device model enable designers to include the spike signal
(caused by the devices’ parasitic capacitance) in the switching
waveforms simulation.
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 30
Time
9.980ms 9.985ms 9.990ms 9.995ms 10.000ms
V(VOUT)
11.9V
12.0V
12.1V
SEL>>
I(L)
0A
2.0A
4.0A
6.0A
I(U2:1)
-2.0A
0A
2.0A
4.0A
6.0A
V(PWM)
0V
5.0V
Spike current
8.Simulation Using Real Device Models (Example)
Time
9.0ms 9.1ms 9.2ms 9.3ms 9.4ms 9.5ms 9.6ms 9.7ms 9.8ms 9.9ms 10.0ms
100* AVG(W(R))/ AVG(-W(Vin))
50
60
70
80
90
100
(9.500m,89.973)
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 31
8.2 Converter Efficiency (Real Device Models)
• The converter efficiency is decreased from 97.3% to 89.97% when the
device models are changed from the near-Ideal to the real model.
Efficiency (%)
Efficiency = 89.97 %
• After the device voltage and current condition is simulated (e.g. VDS, PEAK=12.095V and
ID, PEAK=4.312A), The real device models could be picked up from the SpicePark, that
is the resource of device models, provided by Bee Technologies.
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 32
Maximum Value Device Models
9.SpicePark of MOSFET Model
Simulation Index
All Rights Reserved Copyright (C) Bee Technologies Corporation 2011 33
Simulations Folder name
1. Switching Waveforms......................................................
2. Power Stage Switches Voltage and Current....................
3. Load Transient Response................................................
4. Boost Converter Reliability Testing...................................
5. Converter Efficiency vs. MOSFET Rds(on) ....................
6. Converter Efficiency vs. MOSFET Diode, VF..................
waveforms
powersw
stepload
optimize
efficiency-rdson
efficiency-diode
Libraries :
1. ..\pwmic.lib
2. ..\diode.lib