amplification with anomalous avalanche diodes
TRANSCRIPT
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956 IEEE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, VOL. MTT- 18, NO. 11, NOVEMBER 1970
generation efficiency (6) nor the generation factor (18) ACKNOWLEDGMENT
can be assumed to be constant. The author wishes to thank D. M. Snider, currentlylhus it becomes necessary to be more speeific. Using
the amplifier in Section IV as an example, we could saywith the hl. I.T. Lincoln Laboratory, who suggested the
that its maximum conversion efficiency with a 5-percentproblem and provided the experimental data.
efficient driver along the trajectory defined by Fig. 4 is
8.5 percent. This information is, at least, specific. [1]
Perhaps the best description would be to give the
maximum de-to-RF conversion efficiency that could be p]obtained on a constant output-power trajectory as a
function of the conversion efficiency of the driver.[3]
REFERENCES
D. M. Snider, .4 one-watt CL\T high-efficiency X-band avalanche-diode amplifier, IEEE Trans. Microwave Theory Tech., this issue,pp. 963-967.M. E. Hines, Negative-resistance diode power amplification, IEEE Trans. Electron Devices, vol. ED-1 7, pp. 1-8, January 1970.F. A. Brand, The numbers game, Microwave J., vol. 13, p. 10,July 1970.
Amplification with AnomalousAvalanche Diodes
H. JOHN PRAGER, b5WBER, IEEE, KERN K. N. CHANG, AND S. WEISBROD
AbstractThe experiment described in this paper is performed
for the purpose of obtaining additional information that might help to
elucidate the operating principle of the anomalous mode.The diodes under investigation are of a silicon p+-n-n+ mesa
structure. The breakdown voltage is 160 volts; the punch-through
voltage is 60 volts.
The test setup is similar to a conventional reflection-type ampli-
fier with the diode mounted in a coaxial-cavity-like circuit. Thereverse-bias puke drives the diode to a low avalanche current levelat which anomalous operation would normally commence. In thiscase, however, the tuning and loading of the cavity and its associatedstubs is intentionally arranged to minimize free-runnin g oscillations.Any residual RF power is reduced to the level of weak instabilitieswithout any strong harmonics or subharmonic. Only in the presence
of an input driving power with a frequency at or near the resonancefrequency of the system, does an amplified power of the same fre-quency appear at the output port.
Starting from the residual level the output power increases pro-
portionally with the input power until at higher drives a saturationlevel is reached. In this particular case, operating at 410 MHz, satura-
tion is reached at 18.5 watts with a maximum power gain of 12 dB anda bandwidth of 26 MHz. This output k approximately 20 to 30 dBhigher in amplitude than any observable peak in the residual broad-band frequency spectrum Operating the diode as a free-running~~hmd~~ o scillator at the same current level and frequency, 18.8 Watts
of RF power is obtained.The tiItial and steady-state power levels are substantially the
same for both amplifier and oscillator. A plausible evaluation of theseresults can be obtained following van der Pols differential equation
for a forced negative-resistance oscillator.
Manuscript received April 12, 1970. This work was supported bythe Air Force Avionics Laboratory, Wright-Patterson AFB, Ohio,LI rider AF Contract F33615-68-C-1688, Project 4460.
The authors are with RCA Laboratories, Princeton, N. J. 08540.
introduction
s
I NCE THE discovery of the anomalous avalanche
diode in early 1967 [1], a great deal of effort has
been expended by several laboratories [2 ] [4] not
only to explain the anomaly but also to harness the effect
by developing better diodes and better associated cir-cuitry. While most of these activities concentrated on
the generation of microwave power, relatively little was
done toward the amplification of microwave power. The
first cursory results of amplifier operation were reported
in August 1967 [5]. This was followed by the paper of
Hoefflinger et al., in May 1969 [6], and that of Dienst
et al. [7] who presented the results of their work on a
self-pumped parametric amplifier with the anomalous
avalanche diode. The applications for microwave
amplification are, however, sufficiently important to
warrant still further investigation.
REVIEW OF OSCILLATING OPERATION OF
ANOMALOUS AVALANCHE DIODES
To better highlight the similarities as well as the
differences between oscillator and amplifier perfor-
mance, we shall briefly review some of the pertinent
features of the anomalous diodes as oscillators.
The first successful oscillation of the anomalous
avalanche diode was accomplished in a coaxial circuit as
shown in Fig. 1. The diode was placed in a General
Radio (GR) Tee fitted with proper bypass capacitors,
while stub tuners were used for tuning to the desired fre-
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958 IEEE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, NOVEMBER 1970
,. .
GOLO WIRE
F
CONTACTp+
N
N+
k MEsA DIAMETER 4Fig. 3. Microphotograph of angle-lapped junction.
S LO PE = 0. 4S 0
uULSEGEN,I
Ei00M,SIGGEN
X-TAi v kIRCPL IODBnSCOPEINPUT -
vULSEGE +STUBI--- -*r--f
m
r POWERBo Lo MET ER M ETER3008400 MHzBANDPASSb
-TAL
oSCOPE
OUTPUT,,
Fig. 5. Test setup for avalanche-diode amplifier.
OFF condition. l~hile considerable diode current is al-
ready flowing, the characteristic increase in current is
still missing. llith the input signal OFF there is as yet no
output power present. The right-hand side of Fig. 6
shows the voltage and current when both the diode pulse
and the input signal are turned ON. The diode current
now shows a small but recognizable increase, and the
voltage shows a corresponding dip typical of the
anomalous mode. To prove that these changes are not
due to a switching phenomenon between two unstable
circuit conditions, we gradually varied the input power
and measured the gradual change in output power,
I I I I I I I I II I I I I I I I I II 10 100
I diode current, and diode voltage. The results have been
VOLTAGE (V)
Fig. 4. Capacitance versus reverse voltage,
oscillator, but although the frequency is the same 400
MHz, the stub tuning and matching conditions as well
as the pulse-operating conditions are changed, to meet
the requirements expected from the amplifier. The input
signal is provided by a pulse-modulated RF generator
operating at the same 400-MHz frequency as the circuit
of the diode. The fact that the frequency of the inputcircuit is exactly the same as the resonance of the diode
circuit is an important feature of this amplifier. It
clearly cliff ers in this respect from a self-pumped para-
metric amplifier where there are three separate fre-
quencies for the signal, the pump, and the idler.
The voltage and current waveshapes of the amplifier
are shown in Fig. 6. The left-hand side of the figure
shows the voltage and current of the diode in the
quiescent amplifier condition; i.e., the diode is ON and at
operating levels, but the input signal is zero or in the
plotted in Fig. 7. The voltage aid current did not change
over as wide a range as they did for the oscillator, and
accordingly the efficiency of the amplifier is as yet well
below the efficiency of the oscillator.
To gain a better insight into the working of the
amplifier, we shall now consider the oscilloscope tracings
of Fig. 8. These are measurements of RF power as seen
by the crystal in the detection circuit following the out-
put of the circulator. In Fig. 8(a) the diode is ON, and
the signal is OFF; this means that while the diode was
drawing current, as is shown in the left-hand side of
Fig. 6, practically no RF power was detectable. Ac-
tually with higher scope sensitivity a small RF power ismeasured, and we shall refer to it as (residual 77 RF
power. The minimizing of this residual RF power during
the tuning and adjustment procedure of the amplifier
setup is a very important feature of its performance. Al-
though this procedure is empirical, it is guided by a
basic plan. Briefly it begins by tuning the diode under
self-oscillating conditions to the desired operating fre-
quency of the amplifier. Stub 4 and, to a lesser degree,
stub 3 are the most effective controls in determining
this desired resonance frequency. with the frequency in
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PRAGER et al.: POWER AMPL1F1CATION WITH ANOMALOUS AVALANCHE DIODES959
VOLTAGE
DIODE ON SIGNAL OFF
CURRENT
Fig. 6. Voltage and current pulse waveshapes of amplifier forsignal ON and OFF conditions. Scales: voltage, .50 V/div; current,1 A/div; time, 1 ps/div.
18
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POWER OUTPUT - 14 *
2.5 xn.
tia=a
; 2.4 u \a \z3 \c1
\x
2.L
182I I
183 184 185VOLTAGE, VOLTS
Fig. 7. Pulse current and pulse voltage acrossdiode as function of power output.
the diode circuit thus established, stubs 1, 2, and again
to a lesser degree, stub 3, are now adjusted until the
oscillatory RF power output is minimized and brought
to the lowest attainable residual level. While the first
adjustment sets the frequency, the second adjustment
changes the dynamic load line until a stable amplifier
condition is reached.
Both of these adjustments are required to meet two
necessary conditions of the amplifier, but they are not
sufficient yet, because a further requirement is that the
power output vary gradually (if not linearly) with input.
Thus the next step in the adjustment procedure is to
verify that this continuity requirement has been met or
to modify the stub settings until adequate control has
been accomplished.
Turning our attention to Fig. 8(b), we note that it is
taken with the diode OFF and the signal ON. Since we are
dealing with a reflection-type amplifier, we have of
course the reflected portion of the input power appearing
(a)
(c)
Fig. 8. RF output voltage of amplifier forthree distinct operating conditions.
at the output port. (We hasten, however, to point out
that for the purpose of measuring the power gain of theamplifier, the input power was measured at the input
port and into a 50-ohm load. The picture shown here is
only for the purpose of illustrating the qualitative be-
havior of the amplifier.) In Fig. 8(c) both the diode and
the input signal are ON and a strong RF lpower outputnow makes its appearance.
Looking at the frequency spectrum under the same
three operating conditions, we observe Fig. 9, where the
center frequency in all three cases is 400 MHz. In Fig.
9(a) with the diode ON and the signal OFF, there is again
very little evidence of any residual oscillation at 400
MHz. Fig. 9(b) shows the frequency spectrum with only
the signal ON, and in Fig. 9(c) both the cliode and the
signal are ON simultaneously. Thus we see again that
only in the presence of the signal is the diode driven to
give the desired power output.
In Fig. 10 we have plotted this power output and the
amplifier gain as a function of input power. I t is not a
strictly linear amplification. To begin with, at zero input
power there is a small amount of residual power output
present. Only after very careful adjustment. of the stub
tuners were we able to reduce this residual output to a
bare minimum. But it is of course an essential feature of
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960 IEEE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, NOVEMBER 1970
,POWER OUTPUT
(b)
E ig. 9. Frequency spectrum for amplifier forthree distinct operating conditions.
181 [18
/- ;,6
:~:o .4 .8 1.2 1.6 2.0
POWER INPUT, WATTS
Fig. 10. Power output and gain versus power input.
an ampl if ie r that this residual power be as low as possi-
ble. When we allowed a slightly higher residual level, weachieved a higher power-output level, but also a more
pronounced leveling off at the high end of the curve.
Limitations in the available input-power source pre-
vented further exploration of higher saturation levels.
(This saturation would not be so apparent if the curves
were plotted on loglog paper as is frequently done, and
even the residual power at zero input power would then
conveniently disappear.) Another amplifier character-
istic that is of interest is the bandwidth; this is shown in
Fig. 11. Our amplifier circuit utilizes a narrow-band
FREQUENCY, MHz
Fig. 11. Frequency response curve of amplifier. Power out-put (watts) and power gain (dB) versus frequency (MHz).
1) 400 MHz Z =S.S j5.O 5) 2000 MHz Z=14.5+j16.52) 800 1.0-j2.5 6) 2400 6.5j61.53) 1200 ;: ~~ 7) 2800 8.0 -j754) 1600 . . 8) 3200 1 .0 j 9.0
Fig. 12. Impedence plot for fundamental andharmonic frequencies.
circulator and a triple-stub tuner, which is notoriously
narrow banded. It is therefore not surprising that thetotal bandwidth is only 5.8 MHz or about 1.5 percent.
As part of our experiment we also attempted to mea-
sure the circuit impedance at the point at which the
diode fits into the circuit. For this purpose we removed
the diode from the circuit and replaced it with a 2-inch
length of 50-ohm OSM line which was connected to a
network analyzer. An exact duplicate of this line with a
solid RF short at its end was used to establish and
calibrate the reference point. Fig. 12 gives the results of
these measurements on a Smith chart. The impedance
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PRAGER et al.: POWER AMPLIFICATION WITH ANOMALOUS AVALANCHE DIODSS 961
Fig. 13. Wide-band frequency spectrum of amplifier for signal ON -and OFF conditions.
for the fundamental frequency does not show a very
good match and this might account for the low efficiency
of this particular circuit. The second, third, and fourth
harmonics are typically clustered around a near short
circuit for the real part, and they also show some reac-
tive component. As usual, higher harmonics are much
more reactively terminated.
SPECIAL FREQUENCY STUDY OF THE AMPLIFIER
We had hoped that these amplifier experiments would
not only give us a chance for a feasibility study of the
amplifier per se, but also a chance to collect further data
pertaining to the theoretical model of the anomalousmode. For this purpose we examined the frequency
spectrum of the amplifier, employing a field probe near
the diode and a wide-band spectrum analyzer. This
field probe consisted of a short section of 50-ohm OSM
line and was inserted into the GR Tee through a hole in
its outer shield. The probe was mounted on a microma-
nipulator which allowed precise three-dimensional move-
ment of the probe. Fig. 13 is a composite display of the
wide-band frequency spectrum from O to 6000 MHz, with
each division being 200 MHz. The bottom row shows
the spectrum when the diode is ON and drawing current
and voltage as described before, but with the input
signal turned OFF; consequently, there is no 400-MHztrace present. In the top row both the diode and the
input signal are ON, and a strong trace at 400 MHz as
well as a smaller trace at 800 MHz are now observed.
From our previous results we expected to find a strongfundamental and considerable harmonic content. But
we also found something else: in the signal OFF condition
we observed a small but distinct spectrum line near 1500
MHz and further noticed that this line disappeared in
the signal ON condition. This behavior was unique, since
there was no other frequency just like it. All other fre-
(b)
(c)
Fig. 14. Free-running frequency. (a) For amplifier OFF.(b) For amplifier oN. (c) For oscillator condition.
quency lines show an increase in amplitude when the
input signal is ON. We became very curious about this
frequency and took a closer look at it.Fi~o lA(a) shows this 1.500-MHz line again in the
signal OFF condition; Fig. 14(b) shows the signal ON
condition; and finally in Fig. 14(c) the diode has been
detuned from its amplifier condition until it became an
oscillator at 400 MHz as well as at its harmonics of 800,
1200, and 1600 MHz. And again it can be noted that the
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\b)
14~
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10
8
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0
6
4
4-oo~
POWER OUTPUT AT 400 MHz
(c)
IEEE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, NOVEMBER 1970
Fig. 15. Free-running frequency for amplifier at various levelsof power output. (a) ~e = 1490 MHz; signal OFF. (b) .SignalON.
1500-MHz line has disappeared not only in the ON
condition of the amplifier but also in the oscillator case.
Zooming in still closer to this mysterious frequency, in
Fig. 15 we found it to. be at 1490 MHz. The frequency
dispersion in these pictures is now only 10 MHz/cm.Fig. 15 (a) depicts the signal OFF condition, Fig. 15(b)
shows the signal ON condition, and Fig. 15(c) shows how
the amplitude of the 1490-MHz oscillation decreases as
the power output of the amplifier increases continuously.
The observation of this frequency is quite unexplained
because it does not fit into the expected picture. First,
although the diodes under test should have a transit-
time frequency of approximately 5000 MHz, we could
not find any oscillation near that frequency, and 1490
MHz, is too low to agree with any normal transit-time
calculation. Furthermore, 1490 MHz is not harmon-ically related to the 400 MHz of the input and output
signal. Second, there is the unexplained cause of the
decreasing amplitude of this oscillation with increasing
signal input.
DISCUSSION OF FREQUENCY RESULTS
AND CONCLUSION
In trying to find an explanation for these experimental
results, we turned at first to the present theories of the
anomalous avalanche diode. Typically both the
plasma theory [8] and the avalanche pumped
resonance [6] theory rely on the transit-time frequency
(a)
(b)
(c)
(d)
Fig. 16. Locked oscillator.
oscillation for their starting mechanism and view their
operating frequencies in terms of harmonic relation. The
nonharmonic relation between our signal frequency and
the observed system frequency obviously called for still
further explanations. It was for this reason that van der
Pols classical theory of forced oscillations in a circuit
with nonlinear resistance [9] was given serious con-
sideration. Van der Pol treated both the so-called free
oscillation of the system and its forced oscillation
under the influence of an externally applied signal. He
described how the buildup of the forced oscillation
suppresses the free oscillation and also, significantly for
our interpretation, that these two frequencies do net
have to be harmonically related.
Still unanswered is the exact origin of the free oscilla-
tion of the system. It is however entirely possible that a
transit-time oscillation did exist beyond the calculated
value of 5000 MHz and also beyond the range of our
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IEEE TRANSACTIONS ON MICROWAVE THEORY AND TECHNIQUES, NOVEMBER 1970 963
investigation, i.e., up to 7000 MHz, and that this
transit-time frequency in turn caused a weak anomalous
oscillation at 1490 MHz.
LOCKED OSCILLATOR OPERATION
The type of power amplifier which has been described
here is frequently associated with locked-oscillator
operation. We have therefore endeavored to demon-
strate that type of operation also. This was accomplished
with the same type of diodes used in the amplifier ex-
periments, but the circuit was changed to a simplified
coaxial structure [10 ].
Accordingly, the operating frequency was changed to
1090 MHz. The results are illustrated in Fig. 16, Fig.
16(a) shows the frequency spectrum of the oscillation
before locking, and Fig. 16(b) after locking. The locked-
power output was 25 watts, the locking signal power was
2.5 watts. Fig. 16(c) and (d) show evidence of the fre-
quency locking range with a scale calibration of 1
MHz/cm, thus making the locking range approximately
7 MHz. It should be noted that unlike the amplifier case
there is already a strong oscillation present before the
locking signal is applied and that the change in power
between the unlocked and locked condition is only about
2:1. These two features characterize the two main
differences between a locked oscillator and a power
amplifier.
ACKNOWLEDGMENT
The authors wish to thank Dr. L. S. Nergaard for
suggesting the similarity to van der Pols theory.
[1]
[2]
[3]
REFERENCES
H. J. Prager, K. K. N. Chang, and S. Weisbrod, High-power,high-efficiency silicon avalanche diodes at ultra high fre-quenches, Proc. IEEE (Correspondence), vol. 55, pp. 586-587,April 1967.
R. L. Johnston, D. L. Scharfetter, and D. J. 13artelink, High-efficiency oscillations in germanium avalanche diodes below thetransit-time frequency, Proc. IEEE (Correspondence), vol. 56,pp. 161 11613, September 1968.C. P. Snapp and B. Hoefflinger, An efficient multiresonantavalanche diode oscillator in the 1.5 to 11 G Hz rarwe. Proc.IEEE (Correspondence), vol. 56, pp. 2054-2055, ~ovember1968.
[4] R.- S. Ying, R. G1 Mankarious, and D. L. English, High-effi-ciency anomalous mode oscillation from silicon impatt diodes at6 GHz, 1969 ISSCCDig. Tech. Papers, pp. 86-87.
[5] H. J. Prager, K. K. N. Chang, and S. Weisbrod, Anomaloussilicon avalanche diodes for microwave generation, Proc.Cornell Conf. High F~equency Generation and Amplij cation,pp. 266-280, August 1967.
[6] B. Hoefflinger, C. P. Snapp, and L. A. Stark,, High-efficiencyavalanche resonance Dum~ed amdification. 1969 tit &xo-
[7]
[8]
[9]
[10]
wave Symp. Dig., pp. ~.S5-~60. J. F. Dienst, R. V. DAiello, and E. E. Thomas, Power ampli-fication using an avalanche diode, Electron. Lctt., vol. 5, p. 308,July 1969.A. S. Clorfeine, R. J. Ikola, and L. S. Napoli, A theory for thehigh-efficiency mode of oscillation in avalanche diodes, RCARev., vol. 30, pp. 397-421, September 1969.B. van der Pol, The nonlinear theory of electric oscillations, Proc, IRE+, vol. 22, pp. 1051-1086, September 1934.P. A. Levine and S. G. Liu, Tunable L-band high-power ava-~mc& diode oscdlators, 1969 ISSCC Dig. Tech. Papers, pp.
Correspondence
A One-Watt CW High-Efficiency X-Band Avalanche-
Diode Ampliiier
AbsfracfAn X-band avalanche-diode amplifier circuit is de-scribed which provides accurate and independent in-band impedance
control (R and +Jx) and orthogonal second-harmonic reactance con-
trol. Low-level gains of 13 dB with 500 MHz of bandwidth have been
achieved using thks circuit. Power outputs of 1 watt CW with 5 dB of
gain and 14.7-percent generation efficiency have also been rerdiiedby carefully controlling the in-band and second-harmonic load im-
pedance.Efficient solid-state X-band power generation can be accom-
plished by utilizing the negative-impedance characteristics of ava-lanche diodes in reflection amplifiers. Breadboard 7-GHz circuits have
been constructed which exhibit low-level gains of 13 dB with 500MHz of bandwidth. Power outputs of 1 watt CW, with 5 dB of gainand 14. 7 -percent generation efficiency have been realized in the samecircuit.
The diodes are first characterized by measuring the variation of
small-signal negative impedance with current density and frequency.
Manuscript received March 27, 1970; revised September 7, 1970. This work wassponsored by the Department of the Air Force.
J JpqMe.sucem,ntccuracy * 0 ldSl (Memu ,em,nl Ac, , ,cY i05dS)
4 6 s 10 12 4 6 8 10 12
FREQUENCY (GHz) FREQUENCY (GHz)(a) (b)
Fig. 1. (a) RF +dc port to RF port bias T insertion loss. (b)RF or RF +dc port to dc port bias T isolation.
The diode-pill-package weld flange is used as an impedance reference.A broad-band DC-T is required for this measurement. One was
constructed with the performance shown in Fig. 1 ~1) and (b). A com-puter-controlled network analyzer is used to calibrate out the losses
associated with the DC-T and a So-ohm diode holder. The holder
consists of a 50-ohm coaxial transmission line linearly tapered down
to the dimension of the circuit in which the diode will eventually beplaced. Thermal and electrical ground is provided by the same