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Advanced Control TheoryChibum Lee -Seoultech
Outline
State space solution
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Advanced Control TheoryChibum Lee -Seoultech
Solution of state-space equations
First, recall results for scalar equation:
Laplace transforming:
𝑠𝑋 𝑠 − 𝑥 0 = 𝑎 𝑋 𝑠 + 𝑏 𝑈 𝑠
(𝑠 − 𝑎)𝑋 𝑠 = 𝑥(0) + 𝑏 𝑈 𝑠
Solve for transformed variable:
𝑋 𝑠 =𝑥 0
𝑠 − 𝑎+
𝑏
𝑠 − 𝑎𝑈 𝑠
𝒙 𝒕 = 𝑨𝒙 𝒕 + 𝑩𝒖 𝒕
𝑥 𝑡 = 𝑎 𝑥 𝑡 + 𝑏 𝑢 𝑡
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Advanced Control TheoryChibum Lee -Seoultech
Recall Laplace transform
𝐿−11
𝑠 − 𝑎= 𝑒𝑎𝑡
𝐿−1 𝐹1 𝑠 𝐹2(𝑠) = 0
𝑡
𝑓1 𝑡 − 𝜏 𝑓_2 𝜏 𝑑𝜏
Taking inverse Laplace transform of
𝑥 𝑡 = 𝑒𝑎𝑡𝑥(0) + 0
𝑡
𝑒𝑎 𝑡−𝜏 𝑏𝑢 𝜏 𝑑𝜏
Solution of state-space equations
zero input solution zero state solution
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Advanced Control TheoryChibum Lee -Seoultech
Solution of state-space equations
Vector-matrix equation:
𝒙 𝒕 = 𝑨𝒙 𝒕 + 𝑩𝒖 𝒕
Laplace transforming:
𝒔𝑿 𝒔 − 𝒙 𝟎 = 𝑨 𝑿 𝒔 + 𝑩 𝑼 𝒔
(𝒔𝑰 − 𝑨)𝑿 𝒔 = 𝒙(𝟎) + 𝑩𝑼 𝒔
𝑿 𝒔 = 𝒔𝑰 − 𝑨 −𝟏𝒙(𝟎) + 𝒔𝑰 − 𝑨 −𝟏𝑩𝑼 𝒔
Introducing matrix exponential by analogy with scalar exponential
function
𝑒𝑎𝑡 = 1 +1
1𝑎𝑡 +
1
2!𝑎𝑡 2 +
1
3!𝑎𝑡 3 +
1
4!𝑎𝑡 4 +⋯
𝑒𝐴𝑡 = 𝐼 +1
1𝐴𝑡 +
1
2!𝐴𝑡 2 +
1
3!𝐴𝑡 3 +
1
4!𝐴𝑡 4 +⋯
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Advanced Control TheoryChibum Lee -Seoultech
Ref) Matrix exponential
𝑒𝐴𝑡 matrix exponential
If 𝐴 is an (𝑛 × 𝑛) square matrix, then 𝑒𝐴𝑡 is also an (𝑛 × 𝑛) matrix
From the following (verify!)
1
𝑠 − 𝑎=1
𝑠+
𝑎
𝑠2+𝑎2
𝑠3+𝑎3
𝑠4+⋯
𝑠𝐼 − 𝐴 −1 =𝐼
𝑠+𝐴
𝑠2+𝐴2
𝑠3+𝐴3
𝑠4+⋯
Laplace transform of 𝑒𝐴𝑡 can be found
𝐿−11
𝑠 − 𝑎= 1 +
1
1𝑎𝑡 +
1
2!𝑎𝑡 2 +
1
3!𝑎𝑡 3 +
1
4!𝑎𝑡 4 +⋯ = 𝑒𝑎𝑡
𝐿−1 𝑠𝐼 − 𝐴 −1 = 𝐼 +1
1𝐴𝑡 +
1
2!𝐴𝑡 2 +
1
3!𝐴𝑡 3 +
1
4!𝐴𝑡 4 +⋯ = 𝑒𝐴𝑡
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Advanced Control TheoryChibum Lee -Seoultech
Solution of state-space equations
Note that:
𝐿 𝑒𝐴𝑡 = 𝑠𝐼 − 𝐴 −1
From the previous solution in Laplace domain
𝑿 𝒔 = 𝒔𝑰 − 𝑨 −𝟏𝒙(𝟎) + 𝒔𝑰 − 𝑨 −𝟏𝑩𝑼 𝒔
Taking inverse Laplace transform
𝑥 𝑡 = 𝑒𝐴𝑡𝑥(0) + 0
𝑡
𝑒𝐴 𝑡−𝜏 𝑏𝑢 𝜏 𝑑𝜏
zero input solution zero state solution
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Advanced Control TheoryChibum Lee -Seoultech
State transition matrix
State transition matrix: It describes the transition of the states from
initial conditions 𝑥(0) to those at time 𝑡, when there is no input:
𝒙 𝒕 = 𝚽 𝒕 𝒙(𝟎)
State transition matrix is used to find the solution of linear time varying
system
𝒙 𝒕 = 𝑨(𝒕)𝒙 𝒕 + 𝑩(𝒕)𝒖 𝒕
The matrix exponential 𝑒𝐴𝑡 is the state transition matrix for LTI system
For LTI, Φ 𝑡 satisfies: 𝚽 𝟎 = 𝒆𝑨⋅𝟎 = 𝑰, 𝚽−𝟏 𝒕 = 𝒆−𝑨𝒕 = 𝚽 −𝒕
Other properties of Φ(𝑡): 𝚽 𝒕𝟏 + 𝒕𝟐 = 𝚽 𝒕𝟐 𝚽(𝒕𝟏)
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Advanced Control TheoryChibum Lee -Seoultech
Computation of state transition matrix
In principle, we can compute
• as a series, terminating when no significant change observed
Very simple example: double-integrator plant
• control orientation of satellite with thrusters
States:
S-S:
Φ 𝑡 = 𝑒𝐴𝑡 = 𝐼 +1
1𝐴𝑡 +
1
2!𝐴𝑡 2 +
1
3!𝐴𝑡 3 +⋯
𝐽 𝜃 = 𝐹 ⋅ 𝑑 = 𝑢,Φ 𝑠
𝑈 𝑠=
1
𝐽𝑠2
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Advanced Control TheoryChibum Lee -Seoultech
Computation of state transition matrix
In practice, more
sophisticated numerical
algorithms are employed to
compute the state transition
matrix
Here:
Hence:
Then, solution to homogeneous equation 𝑥 𝑡 = 𝐴𝑥(𝑡) with initial
conditions 𝑥0 = 𝜃0 𝜔0𝑇 is
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Advanced Control TheoryChibum Lee -Seoultech
Ex. State transition matrix via Laplace transform
State transition matrix can be obtained from Laplace transform solution
To illustrate method, consider example plant with transfer function
A state-space realization is
For this system
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𝑠𝐼 − 𝐴 = 𝑠1 01 1
−−3 1−2 0
=𝑠 + 3 −12 𝑠
𝑌(𝑠)
𝑈(𝑠)=
1
𝑠2 + 3𝑠 + 2=
1
(𝑠 + 1)(𝑠 + 2)
𝑥1 𝑥2=
−3 1−2 0
𝑥1𝑥2
+01𝑢
y = 1 0𝑥1𝑥2
Advanced Control TheoryChibum Lee -Seoultech
Ex. State transition matrix via Laplace transform
Hence
Thus
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Φ 𝑠 = 𝑠𝐼 − 𝐴 −1 =
𝑠 1−2 𝑠 + 3𝑠2 + 3𝑠 + 2
=
𝑠
(𝑠 + 1)(𝑠 + 2)
1
(𝑠 + 1)(𝑠 + 2)−2
(𝑠 + 1)(𝑠 + 2)
𝑠 + 3
(𝑠 + 1)(𝑠 + 2)
=
−1
𝑠 + 1+
2
𝑠 + 1
1
𝑠 + 1+
−1
𝑠 + 1−2
𝑠 + 1+
2
𝑠 + 1
2
𝑠 + 1+
−1
𝑠 + 1
Φ 𝑡 = 𝐿−1 𝑠𝐼 − 𝐴 −1 = −𝑒−𝑡 + 2𝑒−2𝑡 𝑒−𝑡 − 2𝑒−2𝑡
−2𝑒−𝑡 + 2𝑒−2𝑡 2𝑒−𝑡 − 𝑒−2𝑡
Advanced Control TheoryChibum Lee -Seoultech
Ex. State transition matrix via Laplace transform
Calculate with MATLAB (Symbolic math)
>>A = [-3 1; -2 0];
>>syms t
>>Phi = expm(A*t)
>>Phi1=subs(Phi,t,1)
Phi =
[ 2*exp(-2*t)-exp(-t), exp(-t)-exp(-2*t)]
[ -2*exp(-t)+2*exp(-2*t), -exp(-2*t)+2*exp(-t)]
can also compute numerical value with MATLAB fn
Phi1 =
-0.0972 0.2325
-0.4651 0.6004
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Φ 𝑡 = 𝐿−1 𝑠𝐼 − 𝐴 −1
= −𝑒−𝑡 + 2𝑒−2𝑡 𝑒−𝑡 − 2𝑒−2𝑡
−2𝑒−𝑡 + 2𝑒−2𝑡 2𝑒−𝑡 − 𝑒−2𝑡
Advanced Control TheoryChibum Lee -Seoultech
Ex. State transition matrix via Laplace transform
Total system response to a unit step input u(t) = 1(t) [U(s) = 1/s] is
applied to the system
Total response is:
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𝑥1 𝑥2=
−3 1−2 0
𝑥1𝑥2
+01𝑢
Advanced Control TheoryChibum Lee -Seoultech
Ex. State transition matrix via Laplace transform
>>A=[-3 1;-2 0]; B=[0;1]; C=[1 0]; D=0;
>>G = ss(A, B, C, D);
>>ltiview(G)
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Advanced Control TheoryChibum Lee -Seoultech
Ex. State transition matrix via Laplace transform
Zero input
response:syms s, syms x10 x20 real
xZI = Phi*[x10; x20]
xZI =
[ (2*exp(-2*t)-exp(-t))*x10+(exp(-t)-exp(-2*t))*x20]
[ (-2*exp(-t)+2*exp(-2*t))*x10+(-exp(-2*t)+2*exp(-t))*x20]
Zero state
Response:
U=1/s;
xZS = ilaplace(inv(s*eye(2)-A)*B*U)
xZS =
[ 1/2-exp(-t)+1/2*exp(-2*t)]
[ 3/2+1/2*exp(-2*t)-2*exp(-t)]
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Advanced Control TheoryChibum Lee -Seoultech
Outline
Simulation diagram
State space realization
• Controllable canonical form
• Observable canonical form
• Modal canonical form
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Advanced Control TheoryChibum Lee -Seoultech
Simulation diagrams
Consider the problem of constructing an analog system to produce a
given input-output behavior, using only integrators, gain elements and
summing elements (as in an ‘analog computer’)
For example, input-output behavior defined by:
Then:
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Advanced Control TheoryChibum Lee -Seoultech
Simulation diagrams
Define states as outputs of integrators
Now we can write the state-space equations:
A state-space realization
A matrix is in upper companion form
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Simulation Diagram vs. Block Diagram
Simulation diagram, in which:
• signals are in the time domain; e.g. 𝑢(𝑡)
• the only system elements are integrators, gains and summers
Block diagram, in which:
• the signals are in the Laplace domain; e.g. 𝑈(𝑠)
• the system elements may be arbitrary transfer functions
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Advanced Control TheoryChibum Lee -Seoultech
Realization
Realization:
For a given LTI system, a state space model which is constructed from
a given transfer function 𝐺 𝑠 is called a realization of 𝐺.
We were able to realize an ODE with no derivatives on the RHS (i.e.,
no zeros in the TF) with a simple chain of integrators
(previous example)
Consider SISO 3rd order model
𝑦 + 𝑎2 𝑦 + 𝑎1 𝑦 + 𝑎0𝑦 = 𝑏2 𝑢 + 𝑏1 𝑢 + 𝑏0𝑢
where 𝑎𝑖 , 𝑏𝑖 are arbitrary real numbers
𝐺 𝑠 =𝑌(𝑠)
𝑈(𝑠)=
𝑏2𝑠2 + 𝑏1𝑠 + 𝑏0
𝑠3 + 𝑎2𝑠2 + 𝑎1𝑠 + 𝑎0
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Advanced Control TheoryChibum Lee -Seoultech
Realization: Controllable canonical form
How to deal with 𝑦 + 𝑎2 𝑦 + 𝑎1 𝑦 + 𝑎0𝑦 = 𝑏2 𝑢 + 𝑏1 𝑢 + 𝑏0𝑢
i.e. 𝐺 𝑠 =𝑌(𝑠)
𝑈(𝑠)=
𝑏2𝑠2+𝑏1𝑠+𝑏0
𝑠3+𝑎2𝑠2+𝑎1𝑠+𝑎0
=𝐵(𝑠)
𝐴(𝑠)
Introduce a partial state 𝜉 as an auxiliary variable, such that:
𝜉 + 𝑎2 𝜉 + 𝑎1 𝜉 + 𝑎0𝜉 = 𝑢 ;Ξ(𝑠)
𝑈(𝑠)=
1
𝐴(𝑠)
• this can be realized with a chain of integrators as before
We can then construct the output thus:
𝑦 = 𝑏2 𝜉 + 𝑏1 𝜉 + 𝑏0𝜉; 𝑌 𝑠 =𝐵 𝑠
𝐴 𝑠𝑈(𝑠) = 𝐵 𝑠 Ξ(𝑠)
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−𝑎2−𝑎1
−𝑎0
𝑏2
𝑏1
𝑏0
Realization: Controllable canonical form
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𝑌(𝑠)
𝑈(𝑠)=
𝑏2𝑠2 + 𝑏1𝑠 + 𝑏0
𝑠3 + 𝑎2𝑠2 + 𝑎1𝑠 + 𝑎0
𝑦 = 𝑏2 𝜉 + 𝑏1 𝜉 + 𝑏0𝜉
𝜉 = 𝑢 − 𝑎2 𝜉 − 𝑎1 𝜉 − 𝑎0𝜉
𝑥1 𝑥2 𝑥3
=−𝑎2 −𝑎1 −𝑎01 0 00 1 0
𝑥1𝑥2𝑥3
+100𝑢
y = 𝑏2 𝑏1 𝑏0
𝑥1𝑥2𝑥3
Advanced Control TheoryChibum Lee -Seoultech
Realization: Observable canonical form
To get another canonical form, rewrite the transfer function
(𝑠3 + 𝑎2𝑠2 + 𝑎1𝑠 + 𝑎0)𝑌 𝑠 = 𝑏2𝑠
2 + 𝑏1𝑠 + 𝑏0 𝑈(𝑠)
Divide throughout by 𝑠3 to obtain
(1 +𝑎2𝑠+𝑎1𝑠2
+𝑎0𝑠3)𝑌 𝑠 =
𝑏0𝑠3
+𝑏1𝑠2
+𝑏0𝑠
𝑈(𝑠)
Rearrange term then,
𝑌 =𝑏0𝑈 − 𝑎0𝑌
𝑠3+𝑏1𝑈 − 𝑎1𝑌
𝑠2+𝑏2𝑈 − 𝑎2𝑌
𝑠
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𝑌(𝑠)
𝑈(𝑠)=
𝑏2𝑠2 + 𝑏1𝑠 + 𝑏0
𝑠3 + 𝑎2𝑠2 + 𝑎1𝑠 + 𝑎0
Advanced Control TheoryChibum Lee -Seoultech
−𝑎2−𝑎1−𝑎0
𝑏2𝑏1𝑏0
Realization: Observable canonical form
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𝑌(𝑠)
𝑈(𝑠)=
𝑏2𝑠2 + 𝑏1𝑠 + 𝑏0
𝑠3 + 𝑎2𝑠2 + 𝑎1𝑠 + 𝑎0
𝑥1 𝑥2 𝑥3
=
−𝑎2 1 0−𝑎1 0 1−𝑎0 0 0
𝑥1𝑥2𝑥3
+
𝑏2𝑏1𝑏0
𝑢
y = 1 0 0
𝑥1𝑥2𝑥3
Advanced Control TheoryChibum Lee -Seoultech
Relationships between CCF and OCF
Observable
canonical
form
Controllable
canonical
form
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Realization: Modal canonical form
If the poles of transfer function are all distinct, we can do the partial
fraction expansion:
Each term in the summation can be represented:
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Advanced Control TheoryChibum Lee -Seoultech
Realization: Modal canonical form
Hence, parallel or diagonal realization:
• The modal states are decoupled
• Output is a linear combination of the system modes
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Realization: Natural modes
We saw previously that by performing a partial fraction expansion of the
transfer function of a dynamic system
• we could obtain a parallel state-space realization
for which the A matrix is diagonal
so that the state-space equations are
decoupled
This modal canonical form is
very fundamental:
• the 'natural modes' make independent
contributions to the system output
• each mode has a characteristic 'natural
frequency' (eigenvalue) and 'mode shape' (eigenvector)
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Natural motions
For 'natural' (unforced) motions (i.e., u ≡ 0):
• We know from before that the unforced response is a combination of simple
exponential motions of the form
• The system is said to be moving in a natural mode when all the states have
the same form of motion:
• The vector 𝒑 (the mode shape) describes the relative amplitude of the
common motion for each state
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Eigenvalue problem
If then
• But
• That is,
• We seek a solution for the eigenvalue (or mode shape) 𝒑.
The condition for a non-trivial solution (i.e., 𝒑 ≠ 0) is that
The roots of the characteristic equation are:
• the "eigenvalues" 𝝀𝒊(i = 1, 2, ..., n) of 𝐴
• the "natural frequencies" of the system
• the "poles" of the transfer function 𝑌(𝑠)/𝑈(𝑠)
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Advanced Control TheoryChibum Lee -Seoultech
Eigenvalue problem
The eigenvalues are the values of λ for which the assumed motion
x(t) = peλt is possible without any external input u
For each eigenvalue λi, we can find the initial conditions x(0) = p
which will excite this natural mode, as the solution of the auxiliary
equation:
The solution p(i) is:
• the "eigenvector" corresponding to the eigenvalue λi
• the "mode shape" of the i-th mode
Note that p(i) may be found easily as a vector proportional to any non-
zero column of the adjugate of the auxiliary matrix F =[λiI −A]
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Example
Auxiliary matrix:
Characteristic equation:
Eigenvalues:
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First mode: λ1 = −2
Auxiliary equation:
Note that the eigenvector, or mode shape, may be normalized in
various ways
• set the first or last element to 1, as above
• set the vector "magnitude" to 1 (unit norm vector):
Solution:
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Rapid calculation of mode shape
Auxiliary matrix:
Adjoint:
• The columns of the adjoint of F are proportional to each other, and to the eigenvector
• It is thus only necessary to compute one column to find the mode shape
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Motion in first natural mode
The first mode may be excited by setting up initial conditions
corresponding to the first mode shape:
Then
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Motion in first natural mode
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Advanced Control TheoryChibum Lee -Seoultech
MATLAB calculation of responses
% Get controller canonical form
>>[A, B, C, D] = tf2ss(1, [1 5 6]);
>>G = ss(A, B, C, D);
% Check
>>G.a
ans =
-5 -6
1 0
% initial condition
>>x0 = [-2 1]';
% compute response
>>[y, t, x] = initial(G, x0);
% plot response
>>plot(t, x), grid
>>legend('x_1', 'x_2')
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Double check with transition matrix solution
% Set up for symbolic computation
>>syms t
>>Phi = expm(A*t) % transition matrix
>>Phi =
[ 3*exp(-3*t)-2*exp(-2*t), -6*exp(-2*t)+6*exp(-3*t)]
[ exp(-2*t)-exp(-3*t), -2*exp(-3*t)+3*exp(-2*t)]
>>x0 = [-2 1]'; % initial condition = mode shape
% Compute zero-input response
>>X = Phi*x0
X =
[ -2*exp(-2*t)]
[ exp(-2*t)]
pure 1st mode
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Second mode: λ2 = −3
Auxiliary equation:
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Motion in second natural mode
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Response to arbitrary initial conditions
Example: Displace 1 unit and release from rest
• Construct initial condition as superposition of mode shapes:
• Then:
Response is the sum of contributions from the independent natural
modes
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Response to initial displacement
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Modal contributions to output y
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Outline
Similarity transform
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Transformations between state variables
We have seen that there is no unique set of state variables to realize a
given input-output behaviour. That is, there are many s-s model for a
given input-output model!!
Given one realization,
We can form another by a (nonsingular) linear transformation of
variables:
T = transformation
matrix
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Advanced Control TheoryChibum Lee -Seoultech
Transformations between state variables
Then:
Hence where
This is called a similarity transformation
Two systems are called equivalent with each other
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Transfer functions from state-space equations
Until now, we have seen that there are many different state space
realizations of a given transfer function
• The reverse process is also of interest; that is, SS TF
Consider a linear time invariant state dynamics
• Start by taking the Laplace Transform of these equations
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Transfer functions from state-space equations
• which gives
• And
• By definition G(s) = C(sI - A)-1B + D is called the Transfer Function of the system.
• And C(sI - A)-1 x(0-) is the initial condition response. It is part of the response, but not part of the transfer function.
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Transfer functions between equivalent models
Let’s get back to two equivalent models
where
Consider the two transfer functions:
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Transfer functions between equivalent models
The transfer function is not changed by putting the state-space model
through a similarity transformation
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Evaluation of transfer function matrix
To evaluate transfer function from s-s model, we should calculate
G(s) = C(sI - A)-1B + D
For a SISO system, G(s) may be evaluated using
For a SIMO system, G(s) may be evaluated using:
See Franklin et al. App C.6
The MATLAB function
ss2tf uses this formulation
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• Choose
Then, state-space equations are:
• Transfer function:
Example
)3)(2(
1
65
1
1
65det
010
01
165
det
2
ssss
s
s
s
s
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Advanced Control TheoryChibum Lee -Seoultech
Let P [p (1) p (2) p (n) ]
And
We have:
Hence:
That is:
Transformation to modal state variables
modal matrix
assume eigenvalues are distinct
The modal matrix P is the similarity
transformation matrix between the original
state vector x and the modal
state vector xd :
54
Advanced Control TheoryChibum Lee -Seoultech
Ex Modal matrix:
Similarity transformation:
modal
canonical
form
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