a dc–5 ghz nmosfet spdt t/r switch in 0.25-μm sige bicmos technology
TRANSCRIPT
A DC–5 GHz NMOSFET SPDT T/R switch in 0.25-mmSiGe BiCMOS technology
Paolo Crippa, Simone Orcioni*, Francesco Ricciardi, Claudio TurchettiDEIT—Dipartimento di Elettronica, Intelligenza Artificiale e Telecomunicazioni,
Universita Politecnica delle Marche, Via Brecce Bianche, I-60131 Ancona, Italy
Abstract
In this paper, the design of a fully integrated DC–5 GHz NMOS single-pole double throw (SPDT) transmit/receive (T/R)
switch for radio-frequency (RF) applications in a 0.25-mm SiGe BiCMOS/RFCMOS technology, is presented. The switch
insertion loss is <1.4 dB, the isolation is >30.1 dB, all over the 0–5 GHz band, and the return loss is >19.9 dB in the 0.8–1 GHz
band and is >10.2 dB in the 0–0.8 GHz and 1–5 GHz bands.
# 2003 Elsevier B.V. All rights reserved.
PACS: 85.40.-e; 85.40.Bh; 84.32.Dd
Keywords: CMOS; RF; SiGe; SPDT; T/R switch
1. Introduction
At present, the dramatic growth of the market of the
wireless and wireline communication systems is put-
ting an increasing pressure on industry to fabricate
low-cost radio-frequency (RF) front-ends. Addition-
ally, the performance requirements of these systems
are steadily increasing as the demand for extremely
large Tx/Rx bandwidth is forcing to use higher and
higher frequency bands. Thus, for those RF front-ends
that adopt time-division duplexing (TDD), high-qual-
ity transmit/receive (T/R) switches are key building
blocks.
In this paper, we describe a fully integrated, 0.25-
mm NMOS single-pole double throw (SPDT) T/R
switch design, for multi-standard/multi-frequency
RF applications working on DC–5 GHz band. This
entirely MOSFET-based SPDT switch uses no inte-
grated inductors thus allowing small die area con-
sumption. In order to make possible the integration of
the switch in a single-chip RF transceiver, it has been
designed in the latest 0.25-mm SiGe RFCMOS process
(i.e. by using the MOS transistors available within the
BiCMOS technology) that is well-suited for low cost,
high volume products. This technology marries the
advantages of silicon–germanium (speed, low noise,
low power consumption) with the CMOS state-of-the-
art in large volume fabrication systems [1]. This
technology offers high-frequency n–p–n bipolar tran-
sistors with fT ¼ 70 GHz and fMAX ¼ 90 GHz, high-
voltage n–p–n bipolar transistors, lateral and vertical
p–n–p transistors, 1.4 kO=& and 50 O=& resistors,
varactor diodes, electrostatic discharge diodes (ESD),
MIM and MOS capacitors, and MOS transistors with
minimum channel length of 0.25 mm. This SPDT
switch, which uses a 3 V power supply, 0–3 V control
Applied Surface Science 224 (2004) 434–438
* Corresponding author. Tel.: þ39-071-220-4543;
fax: þ39-071-220-4835.
E-mail address: [email protected] (S. Orcioni).
0169-4332/$ – see front matter # 2003 Elsevier B.V. All rights reserved.
doi:10.1016/j.apsusc.2003.09.020
voltages, and a 1.6 V of bias voltage, extends all over
the 0–5 GHz band the performances that are usually
achievable only by narrow-band 0.8–1 GHz MOSFET-
based switches.
2. Device design and optimization
Even if bipolar devices are generally faster than
MOS transistors, due to the requirements of a sub-
stantially symmetrical behavior and a high degree of
linearity, NMOSFETs have been chosen as active
devices to implement the SPDT RF T/R switch.
Recent works report narrow-band SPDT switches that
use integrated inductors to improve their impedance
matching and hence their performance. This technique
is not possible in our design, due to the DC–5 GHz
operating frequency range, thus only resistors and
NMOSFETs are used.
Fig. 1 reports the circuit schematic of the switch.
MOS transistors M1 and M2 are used to connect one of
the two unidirectional branches (Tx or Rx) to the
common, bidirectional branch (which we call, for
simplicity, Comm) and to disconnect at the same time
the other unidirectional terminal thus performing the
main switching function. All the MOSFETs are used
as pass-transistors. The control voltage V1 and its
logical complement V2 are used to drive the gates
of the all four MOSFETs. When the switch has a low
insertion loss state between Tx and Comm ports, V1 is
set to 3 V and V2 is set to 0 V. These voltages are
reversed to create a low loss path from the Comm to the
Rx port. The shunt transistors M3 and M4 are used to
improve the isolation of the switch by grounding RF
signals on the side that is turned off. The DC voltage at
all terminals is assumed to be 1:6 V, while the bias
circuit is omitted for simplicity.
The device parameters have been optimized to meet
these goals. The MOSFET’s sizes have been chosen to
obtain high isolation while also maintaining good
values for both the insertion loss and return loss all
over the DC–5 GHz band.
The simplest qualitative approximation for the pass-
transistors in the on-state is an RC network constituted
by a resistor RON and by parasitic capacitances. The
transistor parasitic capacitances CGS, CGD, CDB, and
CSB, shorting the terminals to ground, degrade the per-
formance as frequency raises. A simple method to
partially avoid this negative effect, which acts on CGS
and CGD only, consists of isolating the gate of each
MOSFET from ground by placing a high-valued
impedance (resistor) between the gate and the control
signals. Additionally, the series of the two parasitic
capacitances also slightly improves the insertion loss
bypassing the RON (the admittance 1/RON is quite higher
than the module of the admittances of these parasitic
capacitances).
The sizes of NMOSFETs have been optimized by
considering that increasing the channel width reduces
RON (insertion loss decreases) and increases the capa-
citance coupling to the substrate (insertion loss increa-
ses) by means of CDB and CSB and vice versa [2].
The trade-off results in an aspect ratio of W/L ¼143:7/0.25 mm/mm for the multi-fingered series MOS-
FETs M1 and M2, and in an aspect ratio of W/L ¼ 40/
0.25 mm/mm for the shunt MOSFETs M3 and M4.
2.1. Design at layout level
At the layout level, several test prototypes have
been created, trying not to introduce additional signal-
to-ground parasitic capacitances. In the final layout,
the signals do not travel on excessively wide metal
areas (except the pad), and only top metal layers
(metal4 and metal5) have been used. Additionally,
some metal lines have been shielded from ground in
order to minimize parasitic capacitance to substrate.
We used a 3 V power supply to increase the maximum
voltage swing of the signal: in the best case, if there is
no DC signal component and 0–3 V control voltages
are used, the peak-to-peak input signal can be as high
as 2.5 dB.
M1 M2
M3M4
G1R G2R
G3RG4R
Tx Rx
1V 2V
Comm
Fig. 1. Simplified circuit schematic of the SPDT T/R switch.
P. Crippa et al. / Applied Surface Science 224 (2004) 434–438 435
Fig. 2. Circuit layout (including pads and ESD devices) of the SPDT T/R switch.
Fig. 3. Simulated performances (isolation, return loss, and insertion loss) for the SPDT T/R switch.
436 P. Crippa et al. / Applied Surface Science 224 (2004) 434–438
The Momentum electromagnetic simulator has
been used to analyze the effects of the substrate finite
admittance to ground: there is a non-zero impedance
between substrate and ground. This did not seem to
affect insertion loss, as a higher impedance to ground
in series to the signal-to-substrate parasitics is useful
in this circuit. Only the isolation is degraded by these
parasitics: in fact an ideal isolator would connect the
isolated branch directly to ground, but this is not the
case due to substrate non-ideality.
As a final step, the pad effects (also including the
ESD structures) have been taken into account and
investigated. At the layout level, the pads introduce
large parasitic capacitances: the post-layout simula-
tion has shown a significant performance degradation.
The parasitics have been probed to detect the cause of
the performance drop; it was found that the signal-to-
ground capacitances introduced by the pads were
responsible for it. As a consequence, multiple changes
to the original structure of the signal pads have been
introduced to drastically reduce the signal-to-ground
capacitive coupling: the metal1 shield between the pad
plate and the substrate has been connected to ground
with a 10 kO resistor in order to decrease the signal-to-
ground admittance. These improvements increase the
return loss of 1–1.5 dB; very small improvements have
affected the insertion loss.
The extraction of the ESD diode parasitic capaci-
tances and their inclusion in the post-layout simulation
caused a dramatic performance degradation. The
reduction of both the area and the perimeter of the
diodes has demonstrated to be the only effective way
to solve (at least partially) this problem.
To improve performance a double-well structure
has been used to contain the two switching MOSFETs
M1 and M2, improving their isolation from the sub-
strate. Thus, all the connections to the power supply
and to ground are done through resistors having high
resistance values, to reduce the impact of the parasitic
capacitances associated to the double well. Fig. 2
shows the final layout.
3. Performance description
Using a 0.25-mm single-poly, five-metal SiGe
BiCMOS/RFCMOS technology, 3 V supply, and
0–3 V control voltages, post-layout simulation results
(including the pads and the parasitic components) are
shown in Fig. 3 where isolation, return loss, and
insertion loss of the SPDT T/R switch are reported
as functions of the frequency.
In the DC–2 GHz frequency range, the isolation is
>37.8 dB, the return loss is >16.5 dB, and the inser-
tion loss is <0.96 dB. Although the performances
are degraded at very high frequency, good values
are achieved all over the DC–5GHz frequency
range. These performances are comparable or even
better than those of GaAs SPDT switches or, also,
than those of narrow-band CMOS SPDT switches
[3–5,2].
The achieved performances of the SPDT T/R switch
are summarized below.
Isolation: >30.1 dB (full band).
Return loss: >19.9 dB (@ 0.8–1 GHz).
Return loss: >10.2 dB (@ 0–0.8, and 1–5 GHz).
Insertion loss: <1.4 dB (full band).
4. Conclusions
An NMOS SPDT T/R switch, for multi-standard
multi-frequency RF front-ends operating in the 0–5
GHz frequency range, has been designed and inves-
tigated using a 0.25-mm SiGe BiCMOS/RFCMOS
process. It exhibits a 37:8 dB isolation, a 16:5 dB
return loss, and a 0:92 dB insertion loss at 2 GHz.
Up to 5 GHz isolation is >30.1 dB, return loss is
>10.2 dB, and insertion loss is <1.4 dB.
Acknowledgements
This work was partially supported by Thales Com-
munications S.p.A.
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